
The issue of non-fragile sampled-data control for synchronizing Markov jump Lur'e systems (MJLSs) with time-variant delay was investigated. The time-variant delay allowed for uncertainty that was constrained to an interval with defined upper and lower boundaries. The components of the nonlinear function within the MJLSs were considered to satisfy either Lipschitz continuity or non-decreasing monotonicity. Numerically tractable conditions that ensured stochastic synchronization with a predefined L2−L∞ disturbance attenuation level for the drive-response MJLSs were established, utilizing time-dependent two-sided loop Lyapunov-Krasovskii functionals, together with integral and matrix inequalities. An exact mathematical expression of the desired controller gains can be obtained based on these conditions. Finally, an example with numerical simulation was employed to demonstrate the effectiveness of the proposed control strategies.
Citation: Dandan Zuo, Wansheng Wang, Lulu Zhang, Jing Han, Ling Chen. Non-fragile sampled-data control for synchronizing Markov jump Lur'e systems with time-variant delay[J]. Electronic Research Archive, 2024, 32(7): 4632-4658. doi: 10.3934/era.2024211
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The issue of non-fragile sampled-data control for synchronizing Markov jump Lur'e systems (MJLSs) with time-variant delay was investigated. The time-variant delay allowed for uncertainty that was constrained to an interval with defined upper and lower boundaries. The components of the nonlinear function within the MJLSs were considered to satisfy either Lipschitz continuity or non-decreasing monotonicity. Numerically tractable conditions that ensured stochastic synchronization with a predefined L2−L∞ disturbance attenuation level for the drive-response MJLSs were established, utilizing time-dependent two-sided loop Lyapunov-Krasovskii functionals, together with integral and matrix inequalities. An exact mathematical expression of the desired controller gains can be obtained based on these conditions. Finally, an example with numerical simulation was employed to demonstrate the effectiveness of the proposed control strategies.
Synchronization of chaotic systems stands as a prominent research area within nonlinear system science. Its potential utility spans diverse domains, including the transmission of digital signals, secure communication, and information processing [1,2,3]. Numerous chaotic systems, such as Chua's circuit and Hopfield network, can be effectively represented as Lur'e systems [4]. Consequently, the synchronization of Lur'e systems (LSs) has garnered substantial attention. Within the master-slave framework established by Pecora and Carroll [5], a wealth of research results addressing various synchronization issues, including quasi-synchronization [6], cluster synchronization [7], prespecified-time synchronization [8], and bipartite synchronization [9], have been reported.
In actual engineering systems, abrupt changes can occur in the structure or parameters due to component failures, sudden environmental disturbances, and changes in connections between subsystems. Markov chain often serves as a suitable candidate to model these abrupt change behaviors [10,11,12,13]. Synchronization of Markov jump Lur'e systems (MJLSs) was initially investigated by [14], where a delay feedback control scheme was introduced. Following that, reference [15] considered singular perturbations and developed a mode-dependent control strategy to ensure stochastic synchronization. Reference [16] took into account both time delays and external disturbances, presenting a design for state-feedback controllers to achieve finite-time H∞ synchronization.
Recent years have witnessed the introduction of various networked control strategies, including quantized control [17], event-triggered control [18], and sampled-data control (SDC) [19], in the study of synchronization for MJLSs [20,21,22]. Under SDC strategies, the system's state or output is sampled at specific time instants, and the control action is updated and applied at those discrete time points, thereby effectively decreasing the amount of transmitted information and conserving communication bandwidth [23,24]. In the study of [21], MJLSs with a single time delay were examined. Building on a novel Lyapunov-Krasovskii functional (LKF), two SDC control approaches, formulated in terms of linear matrix inequalities (LMIs), were established to guarantee stochastic synchronization between the master and slave MJLSs. This research was extended to encompass multiple time delays in [22], where a design approach for mean-square exponential synchronization was developed.
Despite theoretical progress in the research of SDC for delayed Markov jump systems, there are still concerns that need to be addressed further. In particular, the time delays are assumed to be time-invariant in [22], whereas, in practical application circumstances, they often display time-variant behavior [25,26]. Incorporating time-variant delays is more challenging but may result in more generic solutions. Furthermore, the control designs in [22] do not account for the influence of gain fluctuations. In engineering implementations, controllers/filters frequently exhibit a degree of parameter inaccuracies due to digital rounding errors, memory constraints, and analog-digital conversion imprecision [27]. As indicated by [28], even a minor gain fluctuation can impair the effectiveness of control/filtering.
Motivated by the preceding discussion, this paper focuses on the issue of non-fragile sampled-data control for synchronizing delayed MJLSs. In contrast to the studies conducted in [21,22], the present research incorporates considerations for both time-variant delay and gain fluctuations. The main contributions of this paper can be summarized as follows: 1) The components of the nonlinear function within the MJLSs are assumed to be either Lipschitz continuous or monotonic nondecreasing. This enables the construction of two distinct two-sided loop LKFs; 2) Two sufficient conditions concerning the non-fragile sampled-data controller design are derived to ensure that the drive-response MJLSs are stochastically synchronized with a prescribed L2−L∞ disturbance attenuation level (DAL). An exact mathematical expression of the desired controller gains can be obtained based on these conditions.
Notations: Throughout, the notation E{⋅} represents the mathematical expectation. col{⋯} and diag{⋯} stand for a column vector and a block-diagonal matrix, respectively. Represent by Rn the n-dimensional Euclidean space, by Rl×n the set of all l×n real matrices, by Sn the n×n symmetric matrices, and by Sn+ the n×n symmetric and positive-define matrices. The superscripts "−1" and "T" stand for the inverse and transpose of a matrix, respectively. S(P) is the sum of matrix P and its transpose (i.e., S(P)=P+PT). λmax(P) is used to denote the largest eigenvalue of P. In and 0l×n represent the n×n identity matrix and l×n zero matrix, respectively. The symbol "∗" denotes a symmetric block.
Consider the following MJLSs with time-variant delay:
{˙x(t)=A(δ(t))x(t)+W(δ(t))x(t−σ(t))+H(δ(t))f(Dx(t)),ˆz(t)=C(δ(t))x(t), | (2.1) |
{˙y(t)=A(δ(t))y(t)+W(δ(t))y(t−σ(t))+H(δ(t))f(Dy(t))+u(t)+G(δ(t))ω(t),ˇz(t)=C(δ(t))y(t), | (2.2) |
where x(t)=col{x1(t),x2(t),…,xn(t)} and y(t)=col{y1(t),y2(t),…,yn(t)} denote the state vectors of the drive and response system, respectively; ˆz(t)=col{ˆz1(t),ˆz2(t),…,ˆzm(t)} and ˇz(t)=col{ˇz1(t),ˇz2(t),…,ˇzm(t)} are the measurement output of the drive and response system, respectively; u(t)∈Rn is the control input; f(Dx(t))=[f1(dT1x1(t)), …, fn(dTnxn(t))] and f(Dy(t))= [f1(dT1y1(t)), …, fn(dTnyn(t))] are nonlinear function vectors, where dTiis the ith row of matrix D; ω(t) denotes the exterior disturbance; and σ(t) is the time delay, which, as in [29,30,31], is considered to be continuous and satisfies the following constraints:
0≤σ1≤σ(t)≤σ2,σ12=σ2−σ1, |
where σ1 and σ2 are the lower and upper bounds of the variable time delay, respectively. System matrices A(δ(t)), W(δ(t)), H(δ(t)), G(δ(t)), and C(δ(t)) are known matrices with appropriate dimensions. x(s)=ˆρ(s) and y(s)=ˇρ(s), s∈[−σ2,0] denote the initial condition with σ2 being the upper bounds of delay function σ(t). The time-homogenous Markov jump process with right continuous trajectories is represented by {δ(t)} that takes values in Γ={1,2,…,˜Γ}. The transition probability matrix (TPM) is characterized by ˜π=πmn, which is defined as follows:
Pr{δ(t+φ)=n|δ(t)=m}={πmnφ+o(φ),m≠n,1+πmmφ+o(φ),m=n, |
where φ>0, limφ→0(o(φ)φ)=0, and πmn, for all m,n∈Γ, denotes the switching rate from m to n with πmn≥0, m≠n, and πmm=−∑˜Γn=1,n≠mπmn<0 [32,33]. The sampled-data controller considered in this study differs from the state-feedback controllers discussed in [34,35,36]. It is based on output feedback and takes into account gain fluctuations. The controller structure is given by:
u(t)=(K(δ(t))+ΔK(δ(t)))(ˆz(tk)−ˇz(tk)), | (2.3) |
where K(δ(t)) denotes the controller gain matrix to be determined and tk (k=0,1,2,…) is the updated instant time of the zero-order-hold [37]. Throughout this work, the sampling periods are considered to be bounded and time-variant, satisfying
tk+1−tk=hk∈[h1,h2], |
where hk denotes the variable sampling interval, and scalars h1 and h2 denote the lower and upper bounds of hk, respectively. ΔK(δ(t)) stands for the gain uncertainty with the following form:
ΔK(δ(t))=E(δ(t))ΘN(δ(t)), | (2.4) |
where E(δ(t)) and N(δ(t)) are certain real constant matrices, and Θ stands for an uncertain matrix meeting ΘTΘ≤I [38,39,40]. Thus, by (2.4), (2.3) can be restructured as
u(t)=(K(δ(t))+E(δ(t))ΘN(δ(t)))(ˆz(tk)−ˇz(tk)). | (2.5) |
For δ(t)=m, m∈Γ, from (2.1), (2.2), and (2.5), we can obtain the following synchronization error system:
˙η(t)=Amη(t)+Wmη(t−σ(t))+Hmf(Dη(t))−(Km+EmΘNm)Cmη(tk)−Gmω(t),t∈[tk,tk+1), | (2.6) |
where f(Dη(t))=f(Dη(t)+Dy(t))−f(Dy(t)). The nonlinear functions are supposed to adhere to one of the two distinct assumptions outlined below:
Assumption 1. There exists a matrix L=diag{Li,…,Ln}>0 that ensures that
|fi(η1)−fi(η2)|≤Li|η1−η2)|,i∈{1,…,n}, |
for any two different scalars η1,η2∈R.
Assumption 2. There exists a matrix L=diag{Li,…,Ln}>0 that ensures that
0≤fi(η1)−fi(η2)η1−η2≤Li,i∈{1,…,n}, |
for any two different scalars η1,η2∈R.
Remark 1. In most extant works discussing systems with nonlinear functions, Assumptions 1 or 2 are two extensively employed hypotheses (see, e.g., [41,42,43]). Assumption 1 imposes a condition on the nonlinear function vector, requiring only Lipschitz continuity of its components. Assumption 2 strengthens this requirement by demanding not only Lipschitz continuity but also nondecreasing monotonicity. Examples of functions that satisfy Assumption 1 but violate Assumption 2 include the cosine function cos(t) and the exponential function exp(−t2).
Definition 1. [44] Error system (2.6) is said to be stochastically stable if, when ω(t)≡0,
∫∞0E{‖η(s)‖2|η0,δ0}ds<∞, |
holds true.
Definition 2. Given a scalar γ>0, drive-response MJLSs (2.1) and (2.2) are said to be stochastically synchronized with a prescribed L2−L∞ DAL γ if error system (2.6) is stochastically stable and
supt≥0E{zT(t)z(t)}≤γ2∫∞0ωT(β)ω(β)dβ, | (2.7) |
holds for all nonzero ω(t)∈L2[0,∞] and the zero initial condition.
The aim of this paper is to figure out a non-fragile sampled-data feedback controller in the compact form of (2.5) to ensure that drive-response MJLSs (2.1) and (2.2) are stochastically synchronized with a prescribed L2−L∞ DAL γ.
The L2−L∞ DAL, also called the energy-to-peak DAL, was proposed by Wilson in [45]. The level is a metric that quantifies the controller's performance to limit the impact of energy-bounded disturbance on the peak of the system's output.
In order to address such an issue, the following four lemmas should be employed:
Lemma 1. [46,47] For a given matrix R∈Sn+ and any differentiable function μ in [λ1,λ2]→Rn, we have
∫λ2λ1˙μT(s)R˙μ(s)ds≥1λ2−λ1ˉΘTdiag{R,3R,5R}ˉΘ, |
where
ˉΘ=[μ(λ2)−μ(λ1)μ(λ2)+μ(λ1)−2λ2−λ1∫λ2λ1μ(s)dsμ(λ2)−μ(λ1)−6λ2−λ1∫λ2λ1υλ1,λ2(s)μ(s)ds],υλ1,λ2(s)=2(s−λ1λ2−λ1)−1. |
Lemma 2. [48] For a scalar β∈(0,1), matrices θ1 and θ2∈Sn+, and θ3 and θ4∈Rn×n, the following inequality holds true:
[θ1β00θ21−β]≥[θ1+(1−β)˜θ1(1−β)θ3+βθ4∗θ2+β˜θ2], |
where ˜θ1=(θ1−θ4θ−12θT4) and ˜θ2=(θ2−θT3θ−11θ3).
Lemma 3. [49] For real matrices R and S of suitable dimensions and a scalar α>0, one has
RST+SRT≤α−1RRT+αSST. |
Lemma 4. [50] The inequality
[RUUTS]>0, |
is equivalent to
S>0 and R−US−1UT>0. |
This section focuses on the non-fragile sampled-data synchronization problem for MJLSs with time-variant delay. Sufficient conditions are provided to ensure stochastic synchronization with a predefined L2−L∞ DAL for the drive-response MJLSs and the corresponding desired controller gains will be given.
To go further, we need to introduce some notations as follows:
pι=[0n×(ι−1)nIn0n×(19−ι)n],ι=1,⋯,19,ˉΩ0=col{p17,p1−p2,p1+p2−2p5,p2−p4,ˆΩ0},ˆΩ0=σ12(p2+p4)−2(p11+p13),ˉΩ1(χ)=col{p1,σ1p5,σ1p6,p11+p13,ˆΩ1(χ)},ˆΩ1(χ)=(σ2−χ)(p11+p14)+(χ−σ1)(p12−p13),Ω2=col{p1−p2,p1+p2−2p5,p1−p2−6p6},Ω3=col{p2−p3,p2+p3−2p7,p2−p3−6p8},Ω4=col{p3−p4,p3+p4−2p9,p3−p4−6p10},Ω34=col{Ω3,Ω4},Ω5=col{p1−p18,p19−p1},Ω6=col{p18,p19},υ0(t)=col{η(t),η(t−σ1),η(t−σ(t)),η(t−σ2)},υ1(t)=1σ1[∫0−σ1ηTt(s)ds∫0−σ1e1(s)ηTt(s)ds]T,υ2(t)=1σ(t)−σ1[∫−σ1−σ(t)ηTt(s)ds∫−σ1−σ(t)e2(s)ηTt(s)ds]T,υ3(t)=1σ2−σ(t)[∫−σ(t)−σ2ηTt(s)ds∫−σ(t)−σ2e3(s)ηTt(s)ds]T,υ4(t)=(σ(t)−σ1)υ2(t),υ5(t)=(σ2−σ(t))υ3(t),ξ(t)=col{ξ0(t),ξ1(t),ξ2(t)},ξ0(t)=col{υ0(t),…,υ5(t)},ξ1(t)=col{f(Dη(t)),ω(t),˙η(t)},ξ2(t)=col{η(tk),η(tk+1)}, |
where ηTt(s)=ηT(t+s) and ej(s)(j=1,⋯,4) are given by
e1(s)=2s+σ1σ1−1,e2(s)=2s+σ(t)σ(t)−σ1−1,e3(s)=2s+σ2σ2−σ(t)−1,e4(s)=2s+σ2σ12−1. |
For the nonlinear function of error system (2.6), we consider the following two different assumptions.
Under Assumption 1, the following inequality holds true
f2i(dTiηi(⋅))≤(LidTiηi(⋅))2,i=1,2,…n. | (3.1) |
In this case, we can propose the following condition:
Theorem 1. Under Assumption 1, for given scalars γ>0, h2≥h1>0, u>0, suppose that there exist scalars ϵm>0, matrices ˜P in S5n+, Pm, S1, S2, R1, R2, S5, S6 in Sn+, S3 in S2n, S4 in Sn, diagonal matrix T5 in Sn+, arbitrary matrices M1, M2 in R3n×3n, M3, M4, T1, S7, S8, Xm in Rn×n, and T3, T4 in R19n×2n, such that
[˜Πhk1(σ1)+ϵmˉNmˉNTmΠ121ˉEm∗Π2210∗∗−ϵmI]<0, | (3.2) |
[˜Πhk1(σ2)+ϵmˉNmˉNTmΠ131ˉEm∗Π2210∗∗−ϵmI]<0, | (3.3) |
[˜Πhk2(σ1)+ϵmˉNmˉNTmΠ122ˉEm∗Π2220∗0−ϵmI]<0, | (3.4) |
[˜Πhk2(σ2)+ϵmˉNmˉNTmΠ132ˉEm∗Π2220∗∗−ϵmI]<0, | (3.5) |
[PmCTm∗γ2I]>0, | (3.6) |
hold for m∈Γ, hk∈{h1,h2}, and χ∈{σ1,σ2}, where
˜Πhk1(χ)=Π0(χ)+ˉT+˘T1+hkˉΛ2−ΩT5ˉΛ1sΩ5,˜Πhk2(χ)=Π0(χ)+ˉT+˘T1+hkˉΛ3−ΩT5ˉΛ2sΩ5,Π121=[(p19−p1)TMT3ΩT3M2],Π131=[(p19−p1)TMT3ΩT4MT1],Π122=[(p1−p18)TM4ΩT3M2],Π132=[(p1−p18)TM4ΩT4MT1],Π221=diag{−S5,−˘R2},Π222=diag{−S6,−˘R2},Π0(χ)=S(pT1Pmp17+ˉΩT1(χ)˜PˉΩ0)+˜Γ∑n=1πmnpT1Pnp1+ˉS+pT17(σ21R1+σ212R2)p17−ΩT2˘R1Ω2−ΩT34˘RTMΩ34+ˉΛ1+T(χ)−pT16p16,ˉS=diag{S1,−S1+S2,0n×n,−S2,015n×15n},˘Ri=diag{Ri,3Ri,5Ri},i={1,2},˘RM=[˘R2+σ2−χσ12˘R2σ2−χσ12M1+χ−σ1σ12M2∗˘R2+χ−σ1σ12˘R2],ˉΛ1s=[S5M4∗2S6],ˉΛ2s=[2S5M3∗S6],ˉΛ1=−(pT1−pT18)S4(p1−p18)+S[(pT19−pT1)S7p19+(pT19−pT1)S8p18],˘T1=S[(pT1T1+pT17uT1)(Amp1+Wmp3+Hmp15−Gmp16−p17)]−S[(pT1+upT17)XmCmp18],T(χ)=S(T3α1(χ)+T4α2(χ)),α1(χ)=(χ−σ1)[p7p8]−[p11p12],α2(χ)=(σ2−χ)[p9p10]−[p13p14],ˉT=(pT1DTLT5LDp1−pT15T5p15),ˉΛ2=−ΩT6S3Ω6+hkpT17S6p17−S(pT17S7p19+pT17S8p18),ˉΛ3=S((pT1−pT18)S4p17)+hkpT17S5p17+ΩT6S3Ω6,ˉEm=−(pT1T1+pT17uT1)Em,ˉNm=NmCmp18. |
Then, drive-response MJLSs (2.1) and (2.2) are stochastically synchronized with a predefined L2−L∞ DAL if the SDC gains in (2.3) are given by
Km=T−11Xm,m∈Γ. | (3.7) |
Proof. For δ(t)=m∈Γ, choose the following LKF:
V(η(t),δ(t),t)=V1(η(t),δ(t),t)+V2(t)+V3(t)+V4(t)+V5(t), [tk,tk+1), | (3.8) |
with
V1(η(t),δ(t),t)=ηT(t)P(δ(t))η(t),V2(t)=ζT1(t)˜Pζ1(t),V3(t)=∫tt−σ1ηT(s)S1η(s)ds+∫t−σ1t−σ2ηT(s)S2η(s)ds,V4(t)=σ1∫0−σ1∫tt+θ˙ηT(s)R1˙η(s)dsdθ+σ12∫−σ1−σ2∫tt+θ˙ηT(s)R2˙η(s)dsdθ,V5(t)=(tk+1−t)(t−tk)ξT2S3ξ2+(tk+1−t)×(η(t)−η(tk))TS4(η(t)−η(tk))+(tk+1−t)hk∫ttk˙ηT(s)S5˙η(s)ds−(t−tk)hk∫tk+1t˙ηT(s)S6˙η(s)ds+2(t−tk)(η(tk+1)−η(t))T×(S7η(tk+1)+S8η(tk)), |
where
ζ1(t)=col{η(t),∫0−σ1ηt(s)ds,∫0−σ1e1(s)ηt(s)ds,∫−σ1−σ2ηt(s)ds,σ12∫−σ1−σ2e4(s)ηt(s)ds}. |
In consideration of
σ12e4(s)=(σ(t)−σ1)e2(s)+(σ2−σ(t))=(σ2−σ(t))e3(s)−(σ(t)−σ1), |
one has
σ12∫−σ1−σ2e4(s)ηt(s)ds=(σ(t)−σ1)(∫−σ1−σ(t)e2(s)ηt(s)ds)−(σ(t)−σ1)(∫−σ(t)−σ2ηt(s)ds)+(σ2−σ(t))(∫−σ1−σ(t)ηt(s)ds)+(σ2−σ(t))(∫−σ(t)−σ2e3(s)ηt(s))=ˆΩ1(σ(t))ξ(t). | (3.9) |
In light of
η(t)=p1ξ(t),∫0−σ1ηt(s)ds=σ1p5ξ(t),∫0−σ1e1(s)ηt(s)ds=σ1p6ξ(t),∫−σ1−σ2ηt(s)ds=(p11+p13)ξ(t), |
and (3.9), we can write
ζT1(t)=ξT(t)ˉΩT1(σ(t)). |
Define L as the infinitesimal generator of random process {η(t),δ(t)}. For each δ(t)=m,
LV(η(t),δ(t),t)=limφ→0+1φ[E{V(η(t+φ),δ(t+φ),t+φ|η(t),δ(t),t)}−V(η(t),δ(t),t)]. |
Subsequently, we can deduce that
LV1(η(t),δ(t),t)=limφ→0+1φ[˜Γ∑n=1,n≠m(πmnφ+o(φ))×ηT(t+φ)Pnη(t+φ)+(1+πmmφ+o(φ))×ηT(t+φ)Pmη(t+φ)−ηT(t)Pmη(t)]=limφ→0+1φ[˜Γ∑n=1(πmnφ+o(φ))ηT(t+φ)Pnη(t+φ)+ηT(t+φ)Pmη(t+φ)−ηT(t)Pmη(t)]=ηT(t)(˜Γ∑n=1πmnPn)η(t)+limφ→0+1φ[ηT(t+φ)Pmη(t+φ)−ηT(t)Pmη(t)]=ηT(t)(˜Γ∑n=1πmnPn)η(t)+2ηT(t)Pm˙η(t). | (3.10) |
It follows that
LV2(t)=ξT(t)S(ˉΩT1(χ)˜PˉΩ0)ξ(t), | (3.11) |
LV3(t)=ξT(t)ˉSξ(t), | (3.12) |
LV4(t)=˙ηT(t)(σ21R1+σ212R2)˙η(t)−σ1∫tt−σ1˙ηT(s)R1˙η(s)ds−σ12∫t−σ1t−σ2˙ηT(s)R2˙η(s)ds, | (3.13) |
LV5(t)=ξT(t)ˉΛ1ξ(t)+ξT(t)((t−tk)ˉΛ2+(tk+1−t)ˉΛ3)ξ(t)−hk∫ttk˙ηT(s)S5˙η(s)ds−hk∫tk+1t˙ηT(s)S6˙η(s)ds. | (3.14) |
For the integral in (3.13), by Lemma 1, one has
−σ1∫tt−σ1˙ηT(s)R1˙η(s)ds≤−ξT(t)ΩT2˘R1Ω2ξ(t), | (3.15) |
−σ12∫t−σ1t−σ2˙ηT(s)R2˙η(s)ds≤−ξT(t)[Ω3Ω4]T[σ12˘R2σ(t)−σ10∗σ12˘R2σ2−σ(t)][Ω3Ω4]ξ(t). | (3.16) |
Employing Jensen's inequality, for the integral items in (3.14), we have
−hk∫ttk˙ηT(s)S5˙η(s)ds≤−hkt−tk(η(t)−η(tk))TS5(η(t)−η(tk)), | (3.17) |
−hk∫tk+1t˙ηT(s)S6˙η(s)ds≤−hktk+1−t(η(tk+1)−η(t))TS6(η(tk+1)−η(t)). | (3.18) |
For any matrices M1, M2 in R3n×3n and M3, M4 in Rn×n, from Lemma 2 we can obtain the following inequalities:
−ξT(t)[Ω3Ω4]T[σ12˘R2σ(t)−σ10∗σ12˘R2σ2−σ(t)][Ω3Ω4]ξ(t)≤−ξT(t)ΩT34˘RMΩ34ξ(t), | (3.19) |
−hkt−tk(η(t)−η(tk))TS5(η(t)−η(tk))−hktk+1−t(η(tk+1)−η(t))TS6(η(tk+1)−η(t))≤−ξT(t)ΩT5[hkt−tkS500hktk+1−tS6]Ω5ξ(t)≤−ξT(t)ΩT5˘SMΩ5ξ(t)≤−ξT(t)ΩT5[t−tkhkˉΛ1s+tk+1−thkˉΛ2s]Ω5ξ(t), | (3.20) |
with
˘SM=[S5+(tk+1−thk)˘SM4(tk+1−thk)M3+t−tkhkM4∗S6+t−tkhk˘SM3],˘SM4=(S5−M4S−16MT4),˘SM3=(S6−MT3S−15M3). |
Furthermore, along (2.6), using the free-weighting-matrix approach [51], for any matrices T1, T2 in Rn×n, the following is satisfied:
0=2[ηT(t)T1+˙ηT(t)T2][Amη(t)+Wmη(t−σ(t))+Hmf(Dη(t))−(Km+EmΘNm)Cmη(tk)−Gmω(t)−˙ηT(t)]. | (3.21) |
On the other hand, by the definitions of α1(σ(t)) and α2(σ(t)), for any matrices T3, T4 in R19n×2n, one has
2ξT(t)(T3α1(σ(t))+T4α2(σ(t)))ξ(t)=0. | (3.22) |
For any diagonal matrix T5 in Sn+, from (3.1), the following holds:
fT(Dη(t))T5f(Dη(t))≤ηT(t)DTLT5LDη(t). | (3.23) |
For t∈[tk,tk+1), combining the above inequalities, one obtains
E{LV(η(t),δ(t),t)}≤E{ξT(t)[t−tkhkΠhk1(σ(t))+tk+1−thkΠhk2(σ(t))]ξ(t)+ωT(t)ω(t)}, |
where
Πhk1(σ(t))=Π0(σ(t))+ˉT+˘T+hkˉΛ2−ΩT5ˉΛ1sΩ5,Πhk2(σ(t))=Π0(σ(t))+ˉT+˘T+hkˉΛ3−ΩT5ˉΛ2sΩ5,˘T=S[(pT1T1+pT17T2)(Amp1+Wmp3+Hmp15−(Km+EmΘNm)Cmp18−Gmp16−p17)]. |
By setting T2=uT1 and using (3.7), Πhk1(σ(t)) can be rearranged as ˜Πhk1(σ(t))+S(ˉEmΘˉNTm). Using Lemma 3, one has
S(ˉEmΘˉNTm)≤ϵ−1mˉEmˉETm+ϵmˉNmˉNTm, |
and, thus, it can be concluded that ˜Πhk1(σ(t))+S(ˉEmΘˉNTm) can be guaranteed by
[˜Πhk1(σ1)+ϵ−1mˉEmˉETm+ϵmˉNmˉNTmΠ121∗Π221]<0, |
which is equivalent to (3.2) by Lemma 4. Since Πhk1(⋅) and Πhk2(⋅) are convex functions, it is easy to get ξT(t)Πhk1(σ(t))ξ(t)<0 from (3.2) and (3.3). Similarly, we can show that ξT(t)Πhk2(σ(t))ξ(t)<0 can be assured by (3.4) and (3.5). Thus, for t∈[tk,tk+1), one has
E{LV(η(t),δ(t),t)}≤E{ωT(t)ω(t)}. | (3.24) |
When ω(t)≡0, from (3.24), there exists a scalar α>0 such that
E{LV(η(t),δ(t),t)}≤−α‖η(t)‖2,tk≤t<tk+1. | (3.25) |
Using Dynkin's formula, one has
E{V(η(t−k+1),δ(t−k+1),tk+1)}−E{V(η(tk),δ(tk),tk)}≤−αE{∫t−k+1tk‖η(s)‖2ds}. | (3.26) |
Since V5(tk)=0 and limt→tkV(η(t),δ(t),t)=V(η(tk),δ(tk),tk), V(η(t),δ(t),t) is continuous. Thus, from (3.26), one obtains
∞∑k=0E{∫t−k+1tk‖η(s)‖2ds}≤α−1E{V(η(0),δ(0),0)}<∞. |
Therefore, from Definition 1, error system (2.6) is stochastically stable.
Next, we consider the case that ω(t)≠0 and introduce a L2−L∞ performance index function of error system (2.6) as follows:
I(t)=E{V(η(t),δ(t),t)}−∫t0ωT(s)ω(s)ds. |
Then, under the zero initial condition, using Dynkin's formula for (3.24) gives
I(t)=E{V(η(0),δ(0),0)}+E{∫t0LV((η(s),δ(s),s)ds}−∫t0ωT(s)ω(s)ds=E{∫t0LV(η(s),δ(s),s)ds−ωT(s)ω(s)ds}. |
From (3.24), one gets I(t)≤0. Thus,
E{V(η(t),δ(t),t)}≤∫t0ωT(s)ω(s)ds. | (3.27) |
Applying Lemma 4, (3.6) is equivalent to
Pm−1γ2CTmCm>0. | (3.28) |
In virtue of (3.8), (3.27), and (3.28), one has
E{zT(t)z(t)}=E{ηT(t)CTmCmη(t)}<E{γ2ηT(t)Pmη(t)}<E{γ2V(η(t),δ(t),t)}<γ2∫t0ωT(s)ω(s)ds<γ2∫∞0ωT(s)ω(s)ds. |
Hence, system (2.6) has a L2−L∞ performance. In this way, the proof is completed.
On the basis of Assumption 2, the following inequalities
f2i(dTiηi(⋅))≤dTiηi(⋅)Lifi(dTiηi(⋅)), | (3.29) |
f2i(dTiηi(⋅))≤(LidTiηi(⋅))2], | (3.30) |
hold true for i=1,…,n.
Based on LKF:
ˉV(η(t),δ(t),t)=V(η(t),δ(t),t)+2n∑i=1∫dTiηi(t)0rifi(s)ds, | (3.31) |
and we can easily derive the following theorem:
Theorem 2. Under Assumption 2, for given scalars γ>0, h2≥h1>0, u>0, suppose that there are scalar ϵm>0, matrices ˜P in S5n+, Pm, S1, S2, R1, R2, S5, S6 in Sn+, S3 in S2n, S4 in Sn, diagonal matrices T5, T6, Λ=diag{r1,…,rn} in Sn+, arbitrary matrices M1, M2 in R3n×3n, M3, M4, T1, S7, S8, Xm in Rn×n, and T3, T4 in R19n×2n, such that the LMIs in (3.6) and
[˜Πhk11(σ1)+ϵmˉNmˉNTmΠ121ˉEm∗Π2210∗∗−ϵmI]<0, | (3.32) |
[˜Πhk11(σ2)+ϵmˉNmˉNTmΠ131ˉEm∗Π2210∗∗−ϵmI]<0, | (3.33) |
[˜Πhk21(σ1)+ϵmˉNmˉNTmΠ122ˉEm∗Π2220∗0−ϵmI]<0, | (3.34) |
[˜Πhk21(σ2)+ϵmˉNmˉNTmΠ132ˉEm∗Π2220∗∗−ϵmI]<0, | (3.35) |
hold for m∈Γ, hk∈{h1,h2}, and χ∈{σ1,σ2}, where
˜Πhk11(χ)=Π0(χ)+ˉT1+˘T1+hkˉΛ2−ΩT5ˉΛ1sΩ5,˜Πhk21(χ)=Π0(χ)+ˉT1+˘T1+hkˉΛ3−ΩT5ˉΛ2sΩ5,Π121=[(p19−p1)TMT3ΩT3M2],Π131=[(p19−p1)TMT3ΩT4MT1],Π122=[(p1−p18)TM4ΩT3M2],Π132=[(p1−p18)TM4ΩT4MT1],Π221=diag{−S5,−˘R2},Π222=diag{−S6,−˘R2},Π0(χ)=S(pT1Pmp17+ˉΩT1(χ)˜PˉΩ0)+˜Γ∑n=1πmnpT1Pnp1+ˉS−ΩT2˘R1Ω2+pT17(σ21R1+σ212R2)p17+T(χ)−ΩT34˘RTMΩ34+ˉΛ1−pT16p16,ˉS=diag{S1,−S1+S2,0n×n,−S2,015n×15n},˘Ri=diag{Ri,3Ri,5Ri},i={1,2},˘RM=[˘R2+σ2−χσ12˘R2σ2−χσ12M1+χ−σ1σ12M2∗˘R2+χ−σ1σ12˘R2],ˉΛ1s=[S5M4∗2S6],ˉΛ2s=[2S5M3∗S6],ˉΛ1=−(pT1−pT18)S4(p1−p18)+S[(pT19−pT1)S7p19+(pT19−pT1)S8p18],˘T1=S[(pT1T1+pT17uT1)(Amp1+Wmp3+Hmp15−Gmp16−p17)]−S[(pT1+upT17)XmCmp18],T(χ)=S(T3α1(χ)+T4α2(χ)),α1(χ)=(χ−σ1)[p7p8]−[p11p12],α2(χ)=(σ2−χ)[p9p10]−[p13p14],ˉT1=S[pT15ΛDp17+(pT1DTL−pT15)T5p15]+pT1DTLT6LDp1−pT15T6p15,ˉΛ2=−ΩT6S3Ω6+hkpT17S6p17−S(pT17S7p19+pT17S8p18),ˉΛ3=S((pT1−pT18)S4p17)+ΩT6S3Ω6+hkpT17S5p17,ˉEm=−(pT1T1+pT17uT1)Em,ˉNm=NmCmp18. |
Then, drive-response MJLSs (2.1) and (2.2) are stochastically synchronized with a predefined L2−L∞ DAL if the SDC gains in (2.3) are given by (3.7).
Proof. For any t∈[tk,tk+1), calculate that
LˉV(η(t),δ(t),t)=LV(η(t),δ(t),t)+2fT(Dη(t))ΛD˙η(t). |
Further, by (3.29) and (3.30), for any diagonal matrices T5, T6 in Sn+, the following hold true:
2[ηT(t)DTL−fT(Dη(t))]T5fT(Dη(t))≥0,ηT(t)DTLT6LDη(t)−fT(Dη(t))T6f(Dη(t))≥0. |
The remainder of the proof is consistent with Theorem 1, which is omitted here.
Remark 2. On the basis of the LMI feasible solutions, Theorems 1 and 2 establish two different conditions for the desired SDC gains, which are capable of being easily verified by publicly accessible MATLAB toolboxes. For a clearer understanding of the proposed controller design, a flowchart is presented in Figure 1. The LKF term 2∑ni=1∫dTiηi(t)0rifi(s)ds is introduced based on Assumption 2, which has the potential to effectively mitigate conservatism. This will be confirmed by comparing the maximum allowable upper bound (MAUB) h2 in the following section.
When there is no gain perturbation (i.e., ΔK(δ(t))=0) and no mode switching (i.e., m=1), (2.3) can be rewritten as u(t)=KCη(tk). Correspondingly, error system (2.6) is simplified to
˙η(t)=Aη(t)+Wη(t−σ(t))+Hf(Dη(t))−KCη(tk)−Gω(t),t∈[tk,tk+1). | (3.36) |
The following criterion can be obtained.
Corollary 1. Under Assumption 1, for given scalars γ>0, h2≥h1>0, u>0, suppose that there are matrices ˜P in S5n+, P, S1, S2, R1, R2, S5, S6 in Sn+, S3 in S2n, S4 in Sn, diagonal matrix T5 in Sn+, arbitrary matrices M1, M2 in R3n×3n, M3, M4, T1, S7, S8, X in Rn×n, and T3, T4 in R19n×2n, such that
[ˉΠhk1(σ1)Π121∗Π221]<0, | (3.37) |
[ˉΠhk1(σ2)Π131∗Π221]<0, | (3.38) |
[ˉΠhk2(σ1)Π122∗Π222]<0, | (3.39) |
[ˉΠhk2(σ2)Π132∗Π222]<0, | (3.40) |
[PCT∗γ2I]>0, | (3.41) |
hold for hk∈{h1,h2} and χ∈{σ1,σ2}, where
ˉΠhk1(χ)=ˉΠ0(χ)+ˉT+˘T2+hkˉΛ2−ΩT5ˉΛ1sΩ5,ˉΠhk2(χ)=ˉΠ0(χ)+ˉT+˘T2+hkˉΛ3−ΩT5ˉΛ2sΩ5,ˉΠ0(χ)=S(pT1Pp17+ˉΩT1(χ)˜PˉΩ0)+ˉS+pT17(σ21R1+σ212R2)p17−ΩT2˘R1Ω2−ΩT34˘RTMΩ34+ˉΛ1+T(χ)−pT16p16,˘T2=S[(pT1T1+pT17uT1)(Ap1+Wp3+Hp15−Gp16−p17)]−S[(pT1+upT17)XCp18],Π121=[(p19−p1)TMT3ΩT3M2],Π131=[(p19−p1)TMT3ΩT4MT1],Π122=[(p1−p18)TM4ΩT3M2],Π132=[(p1−p18)TM4ΩT4MT1],Π221=diag{−S5,−˘R2},Π222=diag{−S6,−˘R2},ˉS=diag{S1,−S1+S2,0n×n,−S2,015n×15n},˘Ri=diag{Ri,3Ri,5Ri},i={1,2},˘RM=[˘R2+σ2−χσ12˘R2σ2−χσ12M1+χ−σ1σ12M2∗˘R2+χ−σ1σ12˘R2],ˉΛ1s=[S5M4∗2S6],ˉΛ2s=[2S5M3∗S6],ˉΛ1=−(pT1−pT18)S4(p1−p18)+S[(pT19−pT1)S7p19+(pT19−pT1)S8p18−(pT1+upT17)XmCmp18],T(χ)=S(T3α1(χ)+T4α2(χ)),α1(χ)=(χ−σ1)[p7p8]−[p11p12],α2(χ)=(σ2−χ)[p9p10]−[p13p14],ˉT=(pT1DTLT5LDp1−pT15T5p15),ˉΛ2=−ΩT6S3Ω6+hkpT17S6p17−S(pT17S7p19+pT17S8p18),ˉΛ3=S((pT1−pT18)S4p17)+ΩT6S3Ω6+hkpT17S5p17,ˉEm=−(pT1T1+pT17uT1)Em,ˉNm=NmCmp18. |
Then, error system (3.36) is stochastically stable and has a predefined L2−L∞ DAL if the SDC gain is determined by K=T−11X.
Corollary 2. Under Assumption 2, for given scalars γ>0, h2≥h1>0, u>0, suppose that there are matrices ˜P in S5n+, P, S1, S2, R1, R2, S5, S6 in Sn+, S3 in S2n, S4 in Sn, diagonal matrix T5 in Sn+, arbitrary matrices M1, M2 in R3n×3n, M3, M4, T1, S7, S8, X, in Rn×n, and T3, T4 in R19n×2n, such that the LMIs in (3.41) and
[ˉΠhk11(σ1)Π121∗Π221]<0, | (3.42) |
[ˉΠhk11(σ2)Π131∗Π221]<0, | (3.43) |
[ˉΠhk21(σ1)Π122∗Π222]<0, | (3.44) |
[ˉΠhk21(σ2)Π132∗Π222]<0, | (3.45) |
hold for hk∈{h1,h2} and χ∈{σ1,σ2}, where
ˉΠhk11(χ)=ˉΠ0(χ)+ˉT1+˘T2+hkˉΛ2−ΩT5ˉΛ1sΩ5,ˉΠhk21(χ)=ˉΠ0(χ)+ˉT1+˘T2+hkˉΛ3−ΩT5ˉΛ2sΩ5,ˉΠ0(χ)=S(pT1Pp17+ˉΩT1(χ)˜PˉΩ0)+ˉS+pT17(σ21R1+σ212R2)p17−ΩT2˘R1Ω2−ΩT34˘RTMΩ34+ˉΛ1+T(χ)−pT16p16,˘T2=S[(pT1T1+pT17uT1)(Ap1+Wp3+Hp15−Gp16−p17)]−S[(pT1+upT17)XCp18],Π121=[(p19−p1)TMT3ΩT3M2],Π131=[(p19−p1)TMT3ΩT4MT1],Π122=[(p1−p18)TM4ΩT3M2],Π132=[(p1−p18)TM4ΩT4MT1],Π221=diag{−S5,−˘R2},Π222=diag{−S6,−˘R2},ˉS=diag{S1,−S1+S2,0n×n,−S2,015n×15n},˘Ri=diag{Ri,3Ri,5Ri},i={1,2},˘RM=[˘R2+σ2−χσ12˘R2σ2−χσ12M1+χ−σ1σ12M2∗˘R2+χ−σ1σ12˘R2],ˉΛ1s=[S5M4∗2S6],ˉΛ2s=[2S5M3∗S6],ˉΛ1=−(pT1−pT18)S4(p1−p18)+S[(pT19−pT1)S7p19+(pT19−pT1)S8p18−(pT1+upT17)XmCmp18],T(χ)=S(T3α1(χ)+T4α2(χ)),α1(χ)=(χ−σ1)[p7p8]−[p11p12],α2(χ)=(σ2−χ)[p9p10]−[p13p14],ˉT1=S[pT15ΛDp17+(pT1DTL−pT15)T5p15]+pT1DTLT6LDp1−pT15T6p15,ˉΛ2=−ΩT6S3Ω6+hkpT17S6p17−S(pT17S7p19+pT17S8p18),ˉΛ3=S((pT1−pT18)S4p17)+ΩT6S3Ω6+hkpT17S5p17,ˉEm=−(pT1T1+pT17uT1)Em,ˉNm=NmCmp18. |
Then, error system (3.36) is stochastically stable and has a predefined L2−L∞ DAL if the SDC gain is determined by K=T−11X.
Consider two-mode (m=1,2) drive-response MJLSs modeled in (2.1) and (2.2) with parameters (refer to [20]):
A1=[−97901−110−14.520],A2=[−187901−110−14.280],W1=[−0.100−0.1000.20−0.1],W2=[−0.0900−0.09000.180−0.09],H1=[18700000000],H2=[27700000000],D=[100000000],C1=C2=[100010001],G1=[0.20000.20000.2],G2=[0.10000.10000.1]. |
Consider the controller gain fluctuation (2.4) with the following parameters:
E1=diag{0.5,0.5,0.5},E2=diag{0.7,0.7,0.7},Θ=col{sin(t),cos(t),sin(t)},N1=N2=0.1. |
The time delay is chosen as σ(t)=0.4+β|sint|, which implies that σ1 and σ2 are 0.4 and 0.4+β, respectively. In addition, the TPM here is assumed to be
˜π=[−0.50.50.8−0.8]. |
In the following, we set u=0.5, h1=0.001, and consider two cases of nonlinear functions:
Case 1: f(Dx(t))=col{12(|x1(t)+1|−|x1(t)−1|),0,0}.
In this case, it's easy to see that f(⋅) satisfies both Assumptions 1 and 2 with L=diag{1,0,0}. The prescribed L2−L∞ performance γ is chosen as 0.25. In view of Theorems 1 and 2, Table 1 details MAUB h2 when σ1 is fixed and β increases from 0.2 to 1.8. As can be seen from Table 1, the MAUB h2 depends on the value of β, and h2 in Theorem 1 is always less than h2 in Theorem 2. Thus, in comparison to Theorem 1, Theorem 2 yields less conservative results. Furthermore, it demonstrates the effectiveness of the intentionally introduced LKF 2∑ni=1∫dTiηi(t)0rifi(s)ds.
β | 0.2 | 0.6 | 1.0 | 1.4 | 1.8 |
Theorem 1 | 0.145 | 0.140 | 0.136 | 0.131 | 0.127 |
Theorem 2 | 0.305 | 0.292 | 0.280 | 0.270 | 0.261 |
Case 2: f(Dx(t))=col{sin(x1),0,0}.
Obviously, the nonlinear function f(⋅) satisfies Assumption 1 but does not satisfy Assumption 2 with L=diag{1,0,0}. Therefore, the proposed condition in Theorem 2 is no longer valid, while the one in Theorem 1 remains applicable. We set h2=0.121 and γ=0.25. By solving the LMIs in Theorem 1, One has
T1=[11.01401.86364.31645.219337.2755−1.31223.91063.19608.9907],X1=[64.318842.909422.447026.7319112.441333.127016.9245−74.627563.2178],X2=[45.317435.618319.123722.7783118.342231.59497.5621−74.028660.5995]. |
Then, the control gain matrices can be obtained as
K1=[6.15658.5683−0.9106−0.17081.37621.2619−0.7347−12.51676.9790],K2=[4.56517.7285−1.1361−0.06761.66371.2458−1.1205−12.18706.7916]. |
For the simulation, we set the initial conditions of the drive-response MJLSs to be x(s)=col{0.2,0.3,0.2}, y(s)=col{−0.3,−0.1,0.4}, s∈[−1.8,0], the external disturbance ω(t)=col{exp(−0.5t), exp(−0.5t), exp(−0.5t)}, and the above parameters. The chaotic behavior of drive system (2.1) with u(t)=0 is shown in Figure 2. Figures 3 and 4 depict the Markov-jump signal and sampling intervals, respectively. Under the designed SDC method, the synchronization between drive-response MJLSs (2.1) and (2.2) is achieved in Figure 5. Figure 6 depicts the trajectories of the error system (2.6). Define a new function
L(t)=√E{zT(t)z(t)}∫t0ωT(β)ω(β)dβ. |
Its evolution versus time is shown in Figure 7. From the figure, one can observe that suptL(t)= 0.0192< γ=0.21, which implies that the prescribed L2−L∞ performance γ is validity guaranteed.
The non-fragile sampled-data synchronization control issue has been studied for MJLSs with time-variant delay. On the foundation of two different assumptions of the nonlinear function vector, two time-dependent two-sided loop LKFs (see (3.8) and (3.27)) have been constructed. By employing these two LKFs and several inequalities, numerically tractable conditions for the design of a non-fragile sampled-data controller (2.5) have been provided in Theorems 1 and 2 to guarantee the drive and response MJLSs realize stochastic synchronization with a prescribed L2−L∞ DAL. Finally, an example has been given to verify the validity of the non-fragile sampled-data controller approaches. In this paper, the transition probabilities of the Markov jump process are assumed to be completely known. In practical applications, however, it is often costly or difficult to obtain all the elements in the TPM. As an extension of the present work, we will further investigate the non-fragile sampled-data synchronization control for Markov jump systems with partially unknown transition probabilities.
The authors declare they have not used Artificial Intelligence (AI) tools in the creation of this paper.
This work was supported by the Natural Science Foundation of the Anhui Higher Education Institutions (Grant No. 2023AH052495).
All authors declare no conflicts of interest in this paper.
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β | 0.2 | 0.6 | 1.0 | 1.4 | 1.8 |
Theorem 1 | 0.145 | 0.140 | 0.136 | 0.131 | 0.127 |
Theorem 2 | 0.305 | 0.292 | 0.280 | 0.270 | 0.261 |