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Research article Special Issues

Adaptive fixed-time stabilization for a class of nonlinear uncertain systems

  • Finite-time stability (FTS) has attained great interest in nonlinear control systems in recent two decades. Fixed-time stability (FxTS) is an improved version of FTS in consideration of its settling time independent of the initial values. In this article, the adaptive fixed-time stabilization issue is studied for a kind of nonlinear systems with nonlinear parametric uncertainties and uncertain control coefficients. Using the adaptive estimate and the adding one power integrator (AOPI) design tool, we propose a two-phase control strategy, which makes that the system states tend to the origin in fixed-time, and other signals are bounded on [0,+). We prove the main results by means of the recently developed fixed-time Lyapunov stability theory. Finally, we apply the proposed adaptive fixed-time stabilizing control strategy into the pendulum system, and the simulation results verify the efficacy of the presented method.

    Citation: Yan Zhao, Jianli Yao, Jie Tian, Jiangbo Yu. Adaptive fixed-time stabilization for a class of nonlinear uncertain systems[J]. Mathematical Biosciences and Engineering, 2023, 20(5): 8241-8260. doi: 10.3934/mbe.2023359

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  • Finite-time stability (FTS) has attained great interest in nonlinear control systems in recent two decades. Fixed-time stability (FxTS) is an improved version of FTS in consideration of its settling time independent of the initial values. In this article, the adaptive fixed-time stabilization issue is studied for a kind of nonlinear systems with nonlinear parametric uncertainties and uncertain control coefficients. Using the adaptive estimate and the adding one power integrator (AOPI) design tool, we propose a two-phase control strategy, which makes that the system states tend to the origin in fixed-time, and other signals are bounded on [0,+). We prove the main results by means of the recently developed fixed-time Lyapunov stability theory. Finally, we apply the proposed adaptive fixed-time stabilizing control strategy into the pendulum system, and the simulation results verify the efficacy of the presented method.



    The fixed-time stabilization studied in this article for the family of nonlinear systems is described by

    {˙ξ1=λ1(t,ξ)ξ2+g1(t,ξ,θ)˙ξj=λj(t,ξ)ξj+1+gj(t,ξ,θ),1jn1˙ξn=λn(t,ξ)u+gn(t,ξ,θ) (1.1)

    with the system state ξ=(ξ1,,ξn)T and the control input uR. The uncertain functions gj:R+×Rn×RnθR,j=1,,n, are continuously differentiable with gj(t,0,θ)=0, t0, and θRnθ represents the unknown constant vector. The continuous functions λj(t,ξ)0 denote the control coefficients, and specifically, λn(t,ξ) is also named as the control direction.

    The objective of this article is to answer the following questions:

    (ⅰ) In the presence of nonlinear parametric uncertainties, is there a globally stabilizing controller that renders the equilibrium x=0 of (1.1) fixed-time globally stable (i.e., global Lyapunov stability with additional properties such as fixed-time convergence)?

    (ⅱ) How to design a fixed-time controller which could render the closed-loop system fixed-time stable without residual sets allowing the nonlinear parametric uncertainties?

    The stabilizing control of nonlinear uncertain systems is one of the most significant tasks in system control. It is noted that the tracking control, output regulation, or disturbance rejection, could be transformed into a stabilization issue by constructing some sort of "error" variable [1]. Asymptotic stabilization together with its enhanced version-exponential stabilization plays a key role in stabilization control for linear or nonlinear systems [2]. The settling time in asymptotic or exponential stabilization is infinite in theory. That is, the system states or tracking error approach to its equilibrium point when the time evolves to infinity. In practice, the finite settling time is obviously more appealing, considering the operation is done in a finite time. It is on this background that the finite-time stability (FTS) is proposed in [7] with the time-optimal control [3]. FTS characterizes that a control system is firstly Lyapunov stable and then exhibits finite-time convergent property of its equilibrium. As noted in [4,5,6], finite-time stability has better performances, such as rapid response, high precision, and robust properties. Currently, the finite-time stabilizing control is still one of the most active topics in the community of nonlinear control systems, see [8,9,10,11,12,13,14,15,16,17,18,19,20,21,22] and the references therein.

    In last several years, a novel variant of FTS, i.e., fixed-time stability (FxTS), is proposed in [23], which is an improved version of finite-time stability. In finite-time stability, the settling time is depending on the system initial values, and it will become large when the initial values are far away from the origin. Fixed-time stability overcomes this drawback, and its settling time is bounded by one fixed constant independent of the initial values [24]. Fixed-time control has some advantages in comparison with finite-time control because the controller could be designed in a manner that its control performance is obtained in a predefined time and regardless to its initial conditions. As a result, fixed-time control displays a better behaviour in the sense that it does not require that the design parameters are re-tuned in order to to maintain the settling time. In recent years, fixed-time control is intensively studied in nonlinear control community, and many interesting results have been reported in this area. For example, the works in [25] and [26] develop the implicit Lyapunov function methodology to investigate the robust FTS and FxTS of nonlinear systems. The work [27] develops a fixed-time terminal sliding mode (TSM) controller for second-order nonlinear perturbed systems. The work in [28] proposes a finite/fixed-time stabilizing control scheme for nonlinear strict-feedback systems using the AOPI technique. The fixed-time control has found its applications in the multi-agent systems (MAS) [29], path-following of automatic vehicles [30,31], nonlinear parametrization [32], nonholonomic systems [33], and robot systems [34], etc.

    Due to the measurement limitations or the modelling errors in practice, the uncertainties are widespread in control systems. As is well known, the adaptive control plays a key role in dealing with parametric uncertainty [35,36,37]. In literature, there have been many results reported in adaptive fixed-time stabilizing control for nonlinear systems with unknown parameters, such as [38,39,40,41,42,43,44], etc. It is pointed out that the existing adaptive control results could not realize the zero error stabilization, that is, the system states does only converge to a small neighborhood of the origin in a given finite time. In fact, a weaker version of fixed-time stability, that is, the practical fixed-time stability is achieved in [40,41,42,43,44]. In view of the unknown parameters in the controlled plants and the finite convergent time regardless to initial values, it brings some residual terms when the control Lyapunov function method is used in control design. This results in that the fixed-time stabilizing without residual sets become extremely difficult. The related methods which effectively handle the adaptive finite-time stability such as [6] and [22] are inapplicable here.

    In this work, we will address the fixed-time stabilizing control with zero residual set for system (1.1). Our aim is to propose a robust adaptive stabilizing controller keeping all the system states globally convergent to zero in some fixed-time. In comparison with the reported results on adaptive fixed-time stabilizing control for uncertain nonlinear systems, the novelties of this article lie in that: 1) This article provides a systematic design of a robust adaptive fixed-time stabilizer to deal with nonlinear parametric uncertainties. The problem of global adaptive fixed-time stabilizing control without residual sets for nonlinear uncertain systems (1.1) is well addressed. 2) We present a constructive procedure to carry out the analysis, since the widely used Barbalat's lemma may fail in nonsmooth feedback control, which brings severe difficulties to the stability analysis in fixed-time control. The constructive analysis gets around this burden, and realizes the zero-error stabilizing control in the presence of unknown parameters in this paper.

    The article is structured as follows. Some preliminaries are provided in Section 2. Section 3 gives the adaptive fixed-time stabilizing control design. Main results are presented in Section 4. Section 5 illustrates the proposed control scheme via a pendulum system. Section 6 concludes the article.

    Notations The following notations will be used in the paper: R denotes the set of real numbers, and Rn denotes the n-dimensional Euclidean space; |a| denotes the absolute value of scalar aR; ξT stands for the transposition of a vector ξRn. For a vector ξ=(ξ1,,ξn)TRn, we denote ˉξi=(ξ1,,ξi)T when i=1,,n, and we let ˉξ1=ξ1 and ˉξn=ξ. The arguments of functions will be sometimes omitted or simplified, for example, a function f(ξ(t)) is denoted by f(ξ) or f() whenever no confusion can arise from the context.

    Take into account the following nonlinear system

    ˙ξ=f(t,ξ),ξ(0)=ξ0,ξRn (2.1)

    with f:[0,)×SRn, h(t,0)=0, and SRn containing the origin.

    Definition 1 [4]: The equilibrium ξ=0 of (2.1) is globally finite-time stable with S=Rn if it is globally asymptotically stable and moreover any trajectory ξ(t,ξ0) of (2.1) arrives at the equilibrium at a finite time instant T(ξ0), i.e., ξ(t,ξ0)=0,tT(ξ0), where T(ξ(0))0 is the settling-time function.

    Definition 2 [23]: The equilibrium ξ=0 of (2.1) is globally fixed-time stable if it is globally finite-time stable and the settling-time function T(ξ0) is bounded by a fixed number, i.e., there is a positive constant Tmax independent of ξ(0) such that T(ξ0)Tmax,ξ0Rn.

    Definition 3: The adaptive fixed-time stabilization problem is to find a continuously differential control law

    {u(t)=μ(ξ(t),χ(t)),μ(0,χ(t))=0,˙χ(t)=ν(ξ(t),χ(t)),ν(0,χ(t))=0, (2.2)

    where μ() and ν() are continuous functions, and χ(t)R is an adaptive variable to estimate the uncertainties, such that the solutions (ξ(t)T,χ(t))T of system (1.1) with controller (2.2) is globally uniformly bounded. Additionally, for any (ξ(0)T,χ(0))TRn+1, ξ(t) converges to its equilibrium in fixed time. That is, for any (ξ(0)T,χ(0))T, there exists a time instant T>0 such that ξ(t)=0 for any t>T, where T is the settling time and does not dependent on (ξ(0)T,χ(0))T.

    We provide some useful lemmas for the following control design and analysis.

    Lemma 1 [28]: For the system: ˙z=c1zhkc2zmn with zR and z(0)=z0, where h, k, m, n are odd positive integers with h<k and m>n, c1>0, and c2>0. Then the origin of system is globally fixed-time stable and its settling time T is bounded by T1c1kkh+1c2mmn.

    Lemma 2 [40]: Suppose that the continuous function W(ξ):RnR is positive definite and radially unbounded satisfying

    ˙W(ξ)c1Wr1(ξ)c2Wr2(ξ)+η, (2.3)

    where c1>0, c2>0, 0<r1<1 and r2>1 and 0<η<. Then, the system (2.1) is practically fixed-time stable. Additionally, the trajectory converges into the residual set given by

    Ω={limtTξ|W(ξ)min{(ηc1(1σ))1r1,(ηc2(1σ))1r2}}, (2.4)

    where 0<σ<1, and the settling time has the following upper bound

    T1c1σ(1r1)+1c2σ(r21). (2.5)

    Lemma 3 [8]: Given 0<ν=mn1 with m,n>0 odd integers, the following holds

    |aνbν|21ν|ab|ν,a,bR. (2.6)

    Lemma 4 [8]: Assume p>0,q>0, pR, qR, and the function ε(a,b)>0, a,bR. Then,

    apbqpε(a,b)|x|p+qp+q+qεpq(a,b)|y|p+qp+q. (2.7)

    Lemma 5 [28]: Assume a1>0,,am>0,b>0, and a1R,,amR,bR, then there holds

    (a1++am)bmax{mb1,1}(ab1++abm). (2.8)

    Throughout this article, we need the following hypothesis.

    Assumption 1: For each gi(t,ξ,θ), there exists a smooth function φi(ξ1,,ξi)0, satisfying

    |gi(t,ξ,θ)|(|ξ1|++|ξi|)φi(ξ1,,ξi)σ, (2.9)

    where σ1 is a constant dependent on θ.

    Assumption 2: The uncertain control coefficients λi(t,ξ) satisfy

    λi1λi(t,ξ)λi2, (2.10)

    where λi1,λi2>0 are known positive real numbers.

    Remark 1: It is noted that the Assumptions 1–2 are commonly used in literature. Assumption 1 shows that x=0 is the equilibrium of (1.1). It is actually a requirement if the stabilizing control without residual sets. This assumption can also be seen in existing works [45,46]. Assumption 2 shows that the uncertain control coefficients λi(t,ξ),i=1,,n, have known lower and upper bounds, which avoids the possible singularity [47].

    Before the control design, we choose the candidate Lyapunov functions in the form of

    Ui=zizi(τ1rizi1ri)2ridτ,1in, (3.1)

    with the following positive real numbers:

    r=4n2n+1,r1=1,rk+22n+1=rk1,k=2,,n+1. (3.2)

    It can be shown that Ui's are positive definite functions (see [8]). In the following control design, we construct the continuously differentiable function

    Wi=ik=1Uk=ik=1zkzk(τ1rkξk1rk)2rkdτ. (3.3)

    Choose the following virtual control laws together as well as the errors

    ξ1=0,z1=ξ1r11ξ11r1,ξ2=1λ11zr21ζ1(ξ1,ˆΨ),z2=ξ1r22ξ21r2,ξn+1=1λn1zrn+1nζn(ξ,ˆΨ),zn=ξ1rnnξn1rn, (3.4)

    and the parameter updating law

    ˙ˆΨ=Γn(ξ,ˆΨ) (3.5)

    with Γ1=zr1L1(ξ1),Γi=Γi1+zriLi(ˉξi,ˆΨ),2in. Particularly, u=ξn+1, ζi()0 and Li()0 are some smooth functions determined later.

    The Propositions 1–6 are used in control design. We provide their proofs in Appendices A–E.

    Proposition 1: Consider

    Wn=nk=1ξkξk(τ1rkξk1rk)2rkdτ, (3.6)

    and one have

    Wn2(z21++z2n). (3.7)

    Proposition 2: One can find a positive number Hi1 satisfying

    λi1(t,ξ)z2ri1i1(ξiξi)14zri1+zriHi1,i=2,,n. (3.8)

    Proposition 3: There is a continuously differentiable function Li1(ˉξi,ˆΨ)0 such that

    z2riigi(t,z,θ)i1j=114zrj+zriLi1(ˉξi,ˆΨ)Ψ,i=2,,n. (3.9)

    Proposition 4: There are positive continuously differentiable functions Hi2(ˉξi1,ˆΨ)0 and Li2(ˉξi,ˆΨ) such that

    i1j=1Uiξj˙ξji1j=114zrj+zriHi2(ˉξi1,ˆΨ)+zriLi2(ˉξi,ˆΨ)Ψ,i=2,,n. (3.10)

    Proposition 5: There exist smooth functions ωi(ˉξi,ˆΨ)0 and ϖi(ˉξi,ˆΨ)0 satisfying

    Γi(ˉξi,ˆΨ)(ij=1zri)ωi(ˉξi,ˆΨ)(ij=1ξri)ϖi(ˉξi,ˆΨ),i=1,,n. (3.11)

    Then, the AOPI method is invoked to show the controller design procedure.

    Step 1: Let

    Ψ=max{σ,σr,σrri,σ1+ri,σ1+1ri,σr2ri,σrr2ri|i=1,,n}. (3.12)

    In what follows, we denote ˆΨ as the estimate of Ψ with the error ˜Ψ=ΨˆΨ.

    We choose the candidate Lyapunov function

    W1=U1+12˜Ψ2. (3.13)

    Then, from (3.1), the time-derivative of W1 along the ξ1-subsystem in (1.1) is

    ˙W1=λ1(t,ξ)ξ1(ξ2ξ2)+λ1(t,ξ)ξ1ξ2+ξ1g1(t,z,θ)˜Ψ˙ˆΨ. (3.14)

    For notational convenience, let L1(ξ1)=z2d1ϕ1(ξ1)0, then, we know from Assumption 1 that

    ξ1g1(t,z,θ)zr1L1(ξ1)ˆΨ+zr1L1(ξ1)˜Ψzr1L1(ξ1)1+ˆΨ2+zr1L1(ξ1)˜Ψ. (3.15)

    Substitute (3.15) into (3.14), and denote ζ1(ξ1,ˆΨ)=n+l1+ˉl1zr0+1r01+L1(ξ1)1+ˆΨ2, with l1>0 a design constant, ˉr=r+r0+1r0, and r0>0 an odd positive integer, and then one get

    ˙W1z1(λ1(t,ξ)ξ2+zr11ζ1(ξ1,ˆΨ))+˜Ψ(zr1L1(ξ1)˙ˆΨ)+λ1(t,ξ)z1(ξ2ξ2)nzr1l1zr1ˉl1zˉr1. (3.16)

    As a result, we choose the following virtual controller

    ξ2=1λ11zr21ζ1(ξ1,ˆΨ), (3.17)

    and from (3.16), we get

    ˙W1nzr1l1zr1ˉl1zˉr1+λ1(t,ξ)z1(ξ2ξ2)+˜Ψ(Γ1˙ˆΨ). (3.18)

    Step i(2in): Suppose that in Step i1, the following holds

    ˙Wi1(n(i2))i1j=1zrji1j=1ljzrji1j=1ˉljzˉrj+(˜Ψ+Ωi1)(Γi1˙ˆΨ)+λi1(t,ξ)z2ri1i1(ξiξi), (3.19)

    where the notation of Ωi1,i=2,,n+1, is defined by

    Ωi1=i1j=1UjˆΨ. (3.20)

    Then, we choose the function

    Wi=ij=1ξjξj(τ1rjξj1rj)2rjdτ+12˜Ψ2, (3.21)

    and in terms of (3.19), its derivative satisfies

    ˙Wi(n(i2))i1j=1zrji1j=1ljzrji1j=1ˉljzˉrj+(˜Ψ+Ωi1)(Γi1˙ˆΨ)+UiˆΨ˙ˆΨ+λi1(t,ξ)z2ri1i1(ξiξi)+i1j=1Uiξj˙ξj+z2riigi(t,z,θ)+λi(t,ξ)z2riiξi+1+λi(t,ξ)z2rii(ξi+1ξi+1). (3.22)

    The following Proposition 6 is used to derive the virtual controller ξi+1, whose proof can be seen in Appendix F.

    Proposition 6: There exists a nonnegative continuous function Hi3(ˉξi,ˆΨ) satisfying

    (˜Ψ+Ωi1)(Γi1˙ˆΨ)+zriLi(ˉξi,ˆΨ)˜Ψ+UiˆΨ˙ˆΨ(˜Ψ+Ωi)(Γi˙ˆΨ)+i1j=114zrj+zriHi3(ˉξi,ˆΨ),i=3,,n. (3.23)

    Define ζi(ˉξi,ˆΨ)=ni+1+li+Hi(ˉξi,ˆΨ)+Li(ˉξi,ˆΨ)1+ˆΨ2+ˉlizr0+1r0i, with Hi(ˉξi,ˆΨ)=Hi1+Hi2(ˉξi1,ˆΨ)+Hi3(ˉξi,ˆΨ) and Li(ˉξi,ˆΨ)=Li1(ˉξi,ˆΨ)+Li2(ˉξi,ˆΨ), li,ˉli>0. Then, the virtual control law is taken as follows

    ξi+1=1λi1zri+1iζi(ˉξi,ˆΨ),i=1,,n. (3.24)

    Substitute (3.24) into (3.22), and one get

    ˙Wi(ni+1)ij=1zrjij=1ljzrjij=1ˉljzˉrj+λi(t,ξ)z2r2i(ξi+1ξi+1)+(˜Ψ+Ωi)(Γi˙ˆΨ). (3.25)

    In particular, we design the actual controller when i=n in (3.24) as follows

    u=ξn+1=1λn1zrn+1nζn(ξ,ˆΨ), (3.26)

    as well as the parameter updating law

    ˙ˆΨ=Γn=ni=1zriLi(ˉξi,ˆΨ). (3.27)

    Then, based on the above calculations, we know that the Lyapunov function

    Wn=nk=1ξkξk(τ1rkξk1rk)2rkdτ+12˜Ψ2 (3.28)

    satisfy

    ˙Wnnk=1zrknk=1lkzrknk=1ˉlkzˉrk. (3.29)

    So far, we complete the adaptive fixed-time stabilizer design.

    Now we summarize the main results contributed in this article in the following Theorem 1.

    Theorem 1: The considered system (1.1) with the adaptive controller (3.26), is globally fixed-time stable in the context of Definition 3.

    Proof: According to (3.28) and (3.29), we can conclude that all solutions (ξ(t),˜Ψ(t)) are bounded. In view of Ψ a constant, it can be concluded that the adaptive estimate ˆΨ(t) is also bounded. Specially, ˆΨ(t)0 if ˆΨ(0)0 according to ˙ˆΨ=Γn(ξ,ˆΨ)0. Then, one can find a positive constant Λ such that

    ˆΨ(t)[0,Λ]. (4.1)

    In accordance of

    Wn=ni=1ξiξi(τ1riξi1ri)2ridτ, (4.2)

    we know from (3.29) that

    ˙Wnni=1zrini=1lizrini=1ˉlizˉri+˜ΨΓn. (4.3)

    Considering d<2 and 2r21<1, we know from Lemma 5 that

    ni=1zri1max{2r21,1}(Wn2)r2=2r2Wnr2. (4.4)

    Similarly, from ˉr>2 and 2ˉr21>1, we have

    ni=1zˉri1max{2ˉr21,1}(ni=1z2i)ˉr2=21ˉrWnˉr2. (4.5)

    For notational convenience, let

    c1=2r2min{l1,,ln},c2=21ˉrmin{ˉl1,,ˉln}, (4.6)

    then, (4.3) turns into

    ˙Wnc1Wnr2c2Wnˉr2ni=1zri+˜ΨΓn. (4.7)

    Define the function

    ˜W(ξ,ˆΨ)=(Ψ+Λ)ωn(ξ,ˆΨ). (4.8)

    According to Proposition 5 with i=n and (4.1), the following calculations hold

    ˙Wnc1Wnr2c2Wnˉr2ni=1zri+(Ψ+Λ)(ni=1zri)ωn(ξ,ˆΨ)=c1Wnr2c2Wnˉr2ni=1zri(1˜W(ξ,ˆΨ)). (4.9)

    In view of

    ˜W(0,ˆΨ)=0,ˆΨ[0,Λ], (4.10)

    and the continuous property of ˜W(ξ,ˆΨ), it is known that there is a real number ρ>0 satisfying for each ξN1 with

    N1={(ξ,ˆΨ):Wn(ξ,ˆΨ)ρ}, (4.11)

    there holds

    ˜W(ξ,ˆΨ)1. (4.12)

    As a result, if (ξ,ˆΨ)N1, that is Wn(ξ,ˆΨ)ρ, in view of the definition of N1, which further implies that

    ˙Wnc1Wnr2c2Wnˉr2. (4.13)

    This shows that once (ξ,ˆΨ)N1, it will be always in N1.

    In what follows, the fixed-time convergence analysis is separated into the following Case Ⅰ and Ⅱ.

    Case Ⅰ: If (ξ(0),ˆΨ(0))N1, it can be seen that, if (ξ,ˆΨ)N1, there holds

    ˙Wnc1Wnr2c2Wnˉr2. (4.14)

    Then, Wn is fixed-time convergent with local property. Since Wn=0 if and only if x=0, according to Lemma 1, one can conclude that x turns to be 0 within T1:

    T11c1(1r2)+1c2(ˉr21). (4.15)

    Clearly, the real constants c1,c2,r,ˉr are independent on the initial values (ξ(0),ˆΨ(0)).

    Case Ⅱ: If (ξ(0),ˆΨ(0))N1, one can calculate its maximum arriving time moment T2 into N1.

    Since ξ, ˆΨ and ˜Ψ are bounded, then there is a real number C>0 satisfying

    ˜ΨΓn(ξ,ˆΨ)C, (4.16)

    which leads to

    ˙Wnc1Wnr2c2Wnˉr2+C. (4.17)

    Motivated by the recent work [40,42], we define the following set:

    N2={(ξ,ˆΨ):Wnmin{(C(1ϵ)c1)2r,(C(1ϵ)c2)2ˉr}} (4.18)

    with any positive constant ϵ(0,1).

    Choose the constants li's and ˉli's large enough, i=1,,n, which in terms of (4.6) renders c1 and c2 large, and further implies (C(1ϵ)c1)2r and (C(1ϵ)c2)2ˉr sufficiently small, such that

    min{(C(1ϵ)c1)2r,(C(1ϵ)c2)2ˉr}ρ, (4.19)

    and then, we can get

    N2N1. (4.20)

    As a result, in view of the Lemma 2, after the fixed-time T1:

    T1=1c1ϵ(1r2)+1c2ϵ(ˉr21), (4.21)

    (ξ,ˆΨ) goes into N2, and hence enters N1. According to the analysis in Case Ⅰ, when (ξ,ˆΨ)N1, after the fixed-time T2:

    T2=1c1(1r2)+1c2(ˉr21), (4.22)

    (ξ,ˆΨ) arrives at zero. Thus, in this situation, ξ approaches the origin within T=T1+T2:

    T=1c1ϵ(1r2)+1c2ϵ(ˉr21)+1c1(1r2)+1c2(ˉr21). (4.23)

    Noting that fact of the positive design parameters c1,c2,r,ˉr irrespective of the initial values, we can see that the closed-loop system states ξ globally converge to zero in fixed-time. Consequently, the problem of global adaptive fixed-time stabilization stated in Definition 3 is well addressed.

    In this subsection, a practical example of a pendulum system is used to illustrate the proposed fixed-time control strategy. It is known that the simple pendulum motion can be described by [48]

    ML¨υ=Mgsin(υ)kL˙υ+1Lu, (5.1)

    where the torque uR is viewed as the control variable, the angular displacement υR is the state. The constants M, L, k, and g denote the mass, length, friction coefficient of the rod, and the gravity acceleration, respectively. It does not require that the parameters M, L, and k are known a priori.

    The control task is to construct a control input torque using the presented control methodology developed here, so that the angular displacement of pendulum is regulated at the angle υ=π in a finite time irrespective of system initial conditions.

    Towards this end, we need the following additional Assumption 3 to characterize the unknown parameters M, L, and k.

    Assumption 3: The parameters m and l are assumed to satisfy

    M_M¯M,L_LˉL. (5.2)

    According to Assumption 3, we have 1¯MˉL21ML21M_L_2.

    To be first, we perform the following coordinates changes

    ξ1=υπ,ξ2=˙υ, (5.3)

    and we get

    {˙ξ1=ξ2˙ξ2=1ML2u+gLsin(ξ1)kMξ2. (5.4)

    It follows that the new system (5.4) has the same form with the considered system (1.1) with g1(t,ξ,θ)=0, g2(t,ξ,θ)=gLsin(ξ1)kMξ2, and θ=max{gL,kM}.

    According to the developed controller design algorithm presented in Section 3, we construct the following adaptive fixed-time controller

    u=¯MˉL2ξr32ζ2(ˉξ2,ˆΨ), (5.5)
    ˙ˆΨ=ξr2L2(ˉξ2,ˆΨ), (5.6)

    with ζ1(ξ1)=2+l1+ˉl1ξr0+1r01, ˆμ1(ξ1,ˆΨ)=ζ1r21(ξ1)+1r2r0+1r0ˉl1ζ1r211(ξ1)ξr0+1r01, ζ2(ˉξ2,ˆΨ)=1+l2+ˉl2ξr0+1r02+H2(ˉξ2, ˆΨ)+L2(ˉξ2,ˆΨ)1+ˆΨ2.

    In simulation, we take the design constants: r1=1,r2=35,r3=15,r=85,r0=5,ˉr=145, and the gain functions: H2(ˉξ2,ˆΨ)=r2r(25)1r22(1r2)(1+r2)r2+(2r2)22(1r2)ˆμ1(ξ1, ˆΨ)+1r(23)r2((2r2)21r2ˆμ1(ξ1,ˆΨ))r, L2(ˉξ2,ˆΨ)=(25)58(1+1r2)r2rξ22r2r2r2+21r2ξ2r2+1r(23)r2(ξ1r22ζ1(ξ1,ˆΨ))1+r2.

    For simulation use, the parameters M, L, and k are chosen as ML2=1, L=g, k=M, and l1=1, l2=0.1, ˉl1=1, ˉl2=0.1, and the initial values ξ1(0)=0.1, ξ2(0)=0.5, ˆΨ(0)=0.5. The simulation results are shown in Figures 12. Particularly, Figure 1 depicts the profiles of the angular displacement υ, its desired angular displacement π, the velocity ˙υ, parameter estimate ˆΨ, and input torque u in (5.1). Figure 2 verifies fixed-time convergence property of the system states in closed-loop system (5.4)–(5.6). From the simulation results, we can see that the designed fixed-time stabilizer could achieve the fixed-time stabilization with zero error for the pendulum.

    Figure 1.  The closed-loop responses of the pendulum system (5.1).
    Figure 2.  The system states of the closed-loop system (5.4)–(5.6).

    The paper presents an adaptive fixed-time stabilization strategy for a kind of nonlinear systems perturbed by nonlinear parametric uncertainty and unknown control coefficients. We combine the adding one power integrator tool and backstepping method to present a systematic fixed-time controller design scheme. The proposed adaptive stabilizer guarantees that the states can converge to its equilibrium in fixed-time, and all closed-loop solutions are bounded. It provides a basic fixed-time stable approach to realize the adaptive stabilizing control for the class of nonlinear uncertain systems with parametric uncertainty and uncertain control coefficients. The obtained result in this article is an improvement of the existing results in the adaptive fixed-time control direction. The simulation results demonstrate the efficacy of the proposed control scheme by means of a pendulum system.

    This work is supported by the National Natural Science Foundation of China under Grant 61803229, the Development Plan of Youth Innovation Team of University in Shandong Province under Grant 2021KJ067, and the National Natural Science Foundation of Shandong Province under Grant ZR2021MF009.

    The authors declare that there is no conflict of interest.

    A. Proof of Proposition 1:

    This proposition can be referred to Proposition 2 together with its proof in [8].

    B. Proof of Proposition 2:

    Using Lemma 3, one can verify that

    λi1(t,ξ)ξ2ri1i1(ξiξi)21riλi1,2|ξ2ri1i1||ξi|ri14ξri1+ξriHi1, (A1)

    with Hi1=rir(r4(2ri1))2ri1ri2(1r2)(2ri1+ri)riλ2ri1+ririi1,2, and then, the proof is completed.

    C. Proof of Proposition 3:

    In terms of Assumption 1 and ξj=1λj1,1ξrij1ζj1(ˉξj1,ˆΨ), j=2,,i, one obtain

    |ξjξj|21rj|ξ1rjjξj1rj|rj=21rj|ξj|rj. (A2)

    Then, there exists a continuous function ˉϕi(ˉξi,ˆΨ)0 such that

    |gi(t,z,θ)|ij=1|ξj|ri+1ˉϕi(ˉξi,ˆΨ)σ. (A3)

    Using Lemma 4, we have the following calculations

    |ξ2rii||ξj|ri+1ˉϕi(ˉξi,ˆΨ)σ14ξrj+ξriLi1(ˉξi,ˆΨ)Ψ, (A4)

    with Li1(ˉξi,ˆΨ)=ij=12rid(d4ri+1)ri+12ri(ˉϕi(ˉξi,ˆΨ))d2ri, and then we complete the proof of proposition.

    D. Proof of Proposition 4:

    Firstly, it can be verified that

    Uiξk=(2ri)(ξi1ri)ξkξiξi(τ1riξi1ri)1ridτ,k=1,,i1. (A5)

    Secondly, we know from ξi=1λi1,1ξrii1ζi1(ˉξi1,ˆΨ) that

    ξi1ri=(1λi1,1)1ri(ξ1ri1i1ξi11ri1)ζ1rii1(ˉξi1,ˆΨ). (A6)

    Thanks to the inductive method, one can find a smooth function ˆμij(ˉξi1,ˆΨ)0 satisfying

    |(ξi1ri)ξj|(i1k=1ξ1rjk)ˆμij(ˉξi1,ˆΨ). (A7)

    Additionally, according to (A7), one get

    (ξi1ri)ξj˙ξj(i1k=1ξ1rjk)ˆμij(ˉξi1,ˆΨ)(λj221rj+1|ξj+1|rj+1+λj2λj1|ξj|rj+1ζj(ˉξj,ˆΨ)+(jk=1|ξk|rj+1)ˉϕj(ˉξj,ˆΨ)σ)(i1k=1ξ1rj+rj+1k)ˆHij(ˉξj,ˆΨ)+(i1k=1ξ1rj+rj+1k)ˆLij(ˉξj,ˆΨ)σ1rj+rj+1rj+1, (A8)

    where ˆHij(ˉξjˆΨ) and ˆLij(ˉξj,ˆΨ) are some nonnegative functions.

    From

    ξiξi(τ1riξi1ri)1ridτ|ξiξi||ξ1riiξi1ri|1ri21ri|ξi|, (A9)

    one can find two nonnegative C1 functions Hi2(ˉξi1,ˆΨ), Li2(ˉξi,ˆΨ), such that

    i1j=1Uiξj˙ξji1j=1(2ri)|ξiξi(τ1riξi1ri)1ridτ||(ξi1ri)ξj˙ξj|i1j=1(2ri)21ri|ξi|((i1k=1ξ1rj+rj+1k)ˆHij(ˉξj,ˆΨ)+(i1k=1ξ1rj+rj+1k)ˆLij(ˉξj,ˆΨ)σ1rj+rj+1rj+1)i1j=114ξrj+ξriHi2(ˉξi1,ˆΨ)+ξriLi2(ˉξi,ˆΨ)Ψ. (A10)

    Then, we complete the proof.

    E. Proof of Proposition 5:

    Firstly, one can choose

    ω1(ξ1,ˆΨ)=ϖ1(ξ1,ˆΨ)=L1(ξ1). (A11)

    Then, the function ωi() can be chosen as ωi(ˉξi,ˆΨ)=max{L1(ξ1),L2(ˉξ2,ˆΨ),,Li(ˉξi,ˆΨ)}, implying

    Γi(ˉξi,ˆΨ)(ξr1++ξri)ωi(ˉξi,ˆΨ),i=2,,n. (A12)

    Considering ξj=1λj1,2ξrjj1ζj1(ˉξj1,ˆΨ), and ξj=ξ1rjjξj1rj, j=2,,i, and then, we have

    ξrj=(ξ1rjjξj1rj)rmax{2d1,1}(ξdrjj+ξjdrj)=ξrj2d1ξ1rjrjdj+2d1(1λj1,2)drjξrj1(ζj1(ˉξj1,ˆΨ))drj. (A13)

    Then, in view of (A13), there exists a nonnegative function ϖi(ˉξi,ˆΨ) satisfying

    Γi(ˉξi,ˆΨ)(ξr1++ξri)ϖi(ˉξi,ˆΨ),i=1,,n. (A14)

    Then, we complete the proof of Proposition 5.

    F. The proof of Proposition 6:

    Firstly, the following holds

    UiˆΨ=(2ri)(ξi1ri)ˆΨξiξi(τ1riξi1ri)1ridτ,i=1,,n. (A15)

    Then, considering ξi1ri=(1λi1,1)1riξi1ζ1rii1(ˉξi1,ˆΨ) and 1ri>1, one can find a smooth function ˆνi(ˉξi,ˆΨ)0 satisfying

    |(ξi1ri)ˆΨ|ˆνi(ˉξi,ˆΨ). (A16)

    Furthermore, it is known from (A9) that

    |UiˆΨ||ξi|(2ri)21riˆνi(ˉξi,ˆΨ). (A17)

    According to Lemma 4, we have

    ξrj|ξi|(2ri)21riˆνi(ˉξi,ˆΨ)ωi(ˉξi,ˆΨ)14ξrj+ξriξrj(r4(r1))(r1)1r((2ri)21riˆνi(ˉξi,ˆΨ)ωi(ˉξi,ˆΨ))r,j=1,,i. (A18)

    Define ˉHi3(ˉξi,ˆΨ)=(ij=1ξrj)(r4(r1))(r1)1r((2ri)21ri ˆνi(ˉξi,ˆΨ)ωi(ˉξi,ˆΨ))r, and then, we know from Proposition 5 that

    |UiˆΨΓi||ξi|(2ri)21riˆνi(ˉξi,ˆΨ)(ij=1ξrj)ωi(ˉξi,ˆΨ)ij=114ξrj+ξriˉHi3(ˉξi,ˆΨ). (A19)

    Let Hi3(ˉξi,ˆΨ)=ˉHi3(ˉξi,ˆΨ)+Li(ˉξi,ˆΨ)(2ri1)21ri11+ξ2i1ˆνi1(ˉξi1,ˆΨ), and one can verify that

    (˜Ψ+Ωi1)(Γi1˙ˆΨ)+ξriLi()˜Ψ+UiˆΨ˙ˆΨ=(˜Ψ+Ωi)(Γi˙ˆΨ)+ξriLi()Ui1ˆΨ+UiˆΨΓi(˜Ψ+Ωi)(Γi˙ˆΨ)+ξriLi()(2ri1)21ri11+ξ2i1ˆνi1(ˉξi1,ˆΨ)+ξriˉHi3(ˉξi,ˆΨ)+i1j=114ξri=(˜Ψ+Ωi)(Γi˙ˆΨ)+ξriHi3(ˉξi,ˆΨ)+i1j=114ξri. (A20)

    Then, the proof is completed.



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