
This paper studies the issue of adaptive fuzzy output-feedback event-triggered control (ETC) for a fractional-order nonlinear system (FONS). The considered fractional-order system is subject to unmeasurable states. Fuzzy-logic systems (FLSs) are used to approximate unknown nonlinear functions, and a fuzzy state observer is founded to estimate the unmeasurable states. By constructing appropriate Lyapunov functions and utilizing the backstepping dynamic surface control (DSC) design technique, an adaptive fuzzy output-feedback ETC scheme is developed to reduce the usage of communication resources. It is proved that the controlled fractional-order system is stable, the tracking and observer errors are able to converge to a neighborhood of zero, and the Zeno phenomenon is excluded. A simulation example is given to verify the availability of the proposed ETC algorithm.
Citation: Chaoyue Wang, Zhiyao Ma, Shaocheng Tong. Adaptive fuzzy output-feedback event-triggered control for fractional-order nonlinear system[J]. Mathematical Biosciences and Engineering, 2022, 19(12): 12334-12352. doi: 10.3934/mbe.2022575
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This paper studies the issue of adaptive fuzzy output-feedback event-triggered control (ETC) for a fractional-order nonlinear system (FONS). The considered fractional-order system is subject to unmeasurable states. Fuzzy-logic systems (FLSs) are used to approximate unknown nonlinear functions, and a fuzzy state observer is founded to estimate the unmeasurable states. By constructing appropriate Lyapunov functions and utilizing the backstepping dynamic surface control (DSC) design technique, an adaptive fuzzy output-feedback ETC scheme is developed to reduce the usage of communication resources. It is proved that the controlled fractional-order system is stable, the tracking and observer errors are able to converge to a neighborhood of zero, and the Zeno phenomenon is excluded. A simulation example is given to verify the availability of the proposed ETC algorithm.
Fractional-order nonlinear systems (FONSs) are a class of complex systems modeled by fractional calculus. In recent years, the application of fractional calculus has attracted wide-ranging attention. In practice, examples such as the blood ethanol concentration system by Qureshi et al. [1], the dynamics of the TB virus by Ullah et al. [2], the fractional Brusselator reaction-diffusion system by Jena et al. [3], etc. can be modeled as fractional order systems. This kind of system can well describe the genetic effect and long memory effect of a real physical system. Nevertheless, it is noteworthy that conventional control scheme is no longer applicable to fractional-order systems due to some general rules for integer-order calculation, such as Chain rules and Leibniz rules, not being well built with regard to fractional derivatives. Hence, how to solve the stability analysis or controller of fractional order systems has attracted extensive attention of scholars. For example, in [4], a fractional order controller designed by Liu et al. to ensure that the synchronization errors of the fractional order chaotic system reached the specified performance whether there is external interference or not. Wei et al. [5] designed an adaptive tracking controller and extended the result to the case of 1<α<2 by the semigroup property of the fractional derivative and fractional tracking differentiator. Afterwards, Li et al. [6] studied the adaptive control issue for a type of commensurate FONS with parametric uncertainty and external interference, and unlike the discontinuous function, the auxiliary function is used to get smooth control input and achieve perfect property tracking in case of bounded interferences. However, the above literature demands that nonlinear functions in the plant are known. So, these techniques are not appropriate for resolving the control issue of FONSs with unknown nonlinear functions.
In practice, there are always completely unknown nonlinear functions in the modeled control systems, which cannot be ignored. Therefore, [7,8,9,10,11] used FLSs or neural networks (NNs) with approximation capability to solve this problem. The authors in [7,8,9] put forward adaptive intelligent (fuzzy and NN) control schemes for FONSs, in which Wang and Liang [8] and Li et al. [9] are robust to input saturation and fault, respectively. Because the above intelligent adaptive control methods adopt a conventional backstepping control technology, there is a problem of computational complexity. In order to avoid this problem, Ma and Ma [10] and Sui et al. [11] proposed several adaptive intelligent state feedback control methods by introducing fractional-order filters. However, the existing methods in [7,8,9,10,11] are merely applicable to those FONSs whose states are only measured. Therefore, the above scheme is not suitable for the control design of FONSs with unmeasurable state variables. Then, [12,13,14] presented some adaptive intelligent output-feedback DSC methods for FONSs with unmeasurable states. It should be noted that in [12], the authors established a new fractional-order reduced-order observer, which not only obtained the information of unmeasurable states, but also reduced errors caused by the full-order state observer in the estimation of some measurable states. As far as we know, there are few results on output-feedback and DSC control simultaneously for fractional-order nonlinear systems, which prompted us to study this problem.
Notably, that the above results adopt conventional periodic control methods, and the control signal needs to be transferred to the actuator in actual time, which will lead to unnecessary sampling and communication. Recently, the ETC theorem has been exploited rapidly, which can reduce the communication load of the controlled system [15,16,17]. An event-triggered pulse control method for impulsive systems is proposed in [15], which successfully solves the stabilization matter of nonlinear impulsive systems and eliminates Zeno behavior. Later, in [16,17], Sui et al. and Wang et al. designed intelligent adaptive ETC schemes for stochastic systems and multi-agent systems to achieve system stability while reducing the waste of communication resources. Note that the systems considered by above intelligent controllers are only applicable to integer-order nonlinear systems, not FONSs. Meanwhile, it is not easy to extend the direct Lyapunov algorithm and its related control schemes from integer order to FONSs. Although [18,19,20] proposed several intelligent adaptive control algorithms for the FONSs, they are designed for situation in which the state is completely measurable and there is a problem of computational complexity. To our knowledge, there is a short age of studies on the observer-based ETC control methods for FONSs, which inspires us to study this problem.
According to the above-mentioned discussions, we study the adaptive output-feedback event-triggered control for FONS with unmeasurable state variables. The proposed ETC scheme can significantly decrease the consumption of communication resources. The main innovations of this paper are as follows.
1) This article first designs an output-feedback event-triggered controller of the FONS. The proposed control algorithm erases the restrictive condition in [18,19,20], with which the state of the system must be completely measured.
2) Due to the DSC technique being used to control design, the put forward control method settles the computational complexity issue in current works [18,19,20].
3) In this paper, the adaptive control law and the event-triggered mechanism are designed together. The stability of the controlled system can be guaranteed by using the fractional-order Lyapunov criterion. Unlike [9,10,11,12], the control signal needs to be sampled and updated regularly. The system drive will be generated only when the preset conditions are met in this paper, which greatly reduces the consumption of network resources.
Consider the following FONS:
C0Dαtxi=xi+1+fi(ˉxi)C0Dαtxn=u+fn(ˉxn)y=x1 | (2.1) |
where ˉxn=[x1,x2,...,xn]T∈Rn are the system state vectors, and y∈R and u∈R denote the output variable and control input of the system. fi(⋅)∈R,i=1,…,n, denotes an unknown smooth nonlinear function. This paper assumes that only the output variable y is measurable.
Assumption 1 [9,10,11,12,13,14]: The given reference signals yd,C0Dαtyd and C0Dαt(C0Dαtyd) are smooth and bounded. Furthermore, assumed that there exists known constant Z0>0 satisfying that y2d+(C0Dαtyd)2+(C0Dαt(C0Dαtyd))2≤Z0.
Control Objectives: In this article, a fuzzy adaptive event-triggered controller is designed for System (1) such that all signals in the considered system are bounded, and the tracking error converges to the compact set of the origin.
Some useful definitions and lemmas are given first.
Definition 1 [21]: The αth Caputo derivative is defined as:
C0DαtF(t)=1Γ(ω−α)∫t0F(ω)(τ)(t−τ)α+1−ωdτ | (2.2) |
where ω−1<α≤ω, ω is a positive integer. Γ(⋅)=∫+∞0τ−1e−τdτ denotes Euler's gamma function with Γ(1)=1.
Definition 2 [21]: The Mittag-Leffler function is formulated as
Eα,ϕ(γ)=∞∑j=0γjΓ(jα+ϕ) | (2.3) |
where α>0,ϕ>0, and γ is a complex number.
Lemma 1 [21]: Let α∈(0,2), η∈R and ϕ∈(πα/2,min{π,πα}), and then one has
Eα,η(ζ)≤r1+|ζ| | (2.4) |
In (2.4), r>0, |ζ|≥0, and ϕ≤|arg(ζ)|≤π.
Lemma 2: Suppose thatf(x) is a continuous function on a compact set Ω. There exists an FLS such as
supx∈Ω|f(x)−ξ∗Tψ(x)|≤ε | (2.5) |
where ε>0 is any positive constant.
Write the FONS (2.1) as follows:
C0Dαtx=Ax+Ky+n∑i=1Bifi(ˉxi)+Buy=Cx | (3.1) |
where A=[−k11⋯0−k20⋯0⋮⋮⋮⋮−kn0⋯0]n×n, K=[k1k2⋮kn]n×1, B=[00⋮1]n×1,Bi=[0⋯1⏟i⋯0]1×n,C=[10⋯0]T,K is chosen such that (A+CK) is a Hurwitz matrix. Q=QT>0 is a positive definite matrix, and exist a positive definite matrix P=PT>0 such that
ATP+PA=−2Q, | (3.2) |
It is worth noting that fi(ˉxi) in (3.1) is an unknown continuous function, so it is necessary to approximate fi(ˉxi) with the help of an FLS ˆfi(ˉxi|ξi)=ξTiϕi(ˉxi),. In the bounded sets Ω, the definition of ideal parameter vectors ξ∗i are described as:
ξ∗i=argminξ∈Ω[supˉxi∈U|ˆfi(ˉxi|ξi)−fi(ˉxi)|] | (3.3) |
The definition of the optimal approximation errorεi is described as
εi=fi(ˉxi)−ˆfi(ˉxi|ξ∗i) | (3.4) |
with εi(ˉxi) is bounded by constant ε∗i>0.
Design the fuzzy state observer for (3.1) as
C0Dαtˆx=Aˆx+Ky+n∑i=1Biˆfi(ˆˉxi|ξi)+Buˆy=Cˆx | (3.5) |
where ˆx=[ˆx1,ˆx2,…,ˆxn]T are the estimations of x.
Define the observer error as e=x−ˆx.
From (3.1), (3.4) and (3.5), one has
C0Dαte=n∑i=1Biξ∗Ti(ϕi(ˉxi)−ϕi(^¯xi))+Ae+n∑i=1Bi˜ξTiϕi(^¯xi)+ε | (3.6) |
where ε=[ε1,ε2,…,εn]T,ξi are the estimations of ideal parameters ξ∗i, and ˜ξ=ξ∗−ξ.
Construct the Lyapunov function candidate as V0=12eTPe, and then the following Theorem can be obtained.
Theorem 1: For controlled System (2.1), the fuzzy state observer (3.3) has the following property:
C0DαtV0≤−λ0||e||2+12||P||2n∑i=1||˜ξi||2+δ0 | (3.7) |
where λ0=(λmin(Q)−2)>0, and δ0=||P||2∑ni=1||ξ∗i||2+12||P||2∑ni=1ε∗2i.
Proof: We choose the Lyapunov function candidate as V0=12eTPe. From (3.5) and (3.6), by the inequality C0Dαt(xT(t)x(t))/2≤xT(t)C0Dαtx(t), C0DαtV0 can be calculated as
C0DαtV0≤12eT(PA+ATP)e+eTP(n∑i=1Biξ∗Ti(ψi(ˉxi)−ψi(^¯xi))+n∑i=1Bi˜ξTiψi(ˆˉxi)+ε), | (3.8) |
By employing Young's inequality and ψTi(ˆxi)ψi(ˆxi)≤1, we can gain
eTP(n∑i=1Biξ∗Ti(ψi(ˉxi)−ψi(^¯xi))≤‖e‖2+‖P‖2∑ni=1‖ξ∗i‖2eTPn∑i=1Bi˜ξTiψi(^¯xi)≤12‖e‖2+12‖P‖2∑ni=1˜ξTi˜ξieTPε≤12‖e‖2+12‖P‖2∑ni=1ε∗2i | (3.9) |
Substituting (3.9) into (3.8), one can have (3.7). This completes the proof of Theorem 1.
Remark 1: Theorem 1 shows that if ˜ξTi˜ξi is bounded, smaller observation errors ei can be obtained by selecting a large enough λ0. It is further concluded that the constructed fuzzy state observer (3.5) can better estimate the unknown states.
This part will use the adaptive fuzzy backstepping control algorithm to provide the observer-based adaptive ETC control design program and give its stability analysis.
Make the coordinate transforms as
S1=x1−ydSi=ˆxi−υi−1i=2,…,nηi−1=υi−1−τi−1 | (4.1) |
where S1 is tracking error, Si are dynamic surface errors, υi are filter variables, and ηi are filter output errors, and τi−1 are the virtual control functions.
Step1: Via (3.3), (4.1), and x2=e2+ˆx2, one has
C0DαtS1=x2+f1(x1)−C0Dαtyd=e2+S2+η1+τ1+ξ∗T1(ϕ1(x1)−ϕ1(ˆx1))+ξT1ϕ1(ˆx1)+˜ξT1ϕ1(ˆx1)−C0Dαtyd+ε1 | (4.2) |
Choose the Lyapunov function as
V1=V0+12S21+12γ1˜ξT1˜ξ1 | (4.3) |
where γ1>0 is a known constant.
The virtual controller τ1 and the adaptive law C0Dαtξ1 are designed as
τ1=−c1S1−52S1−ξT1ϕ1(ˆx1)+C0Dαtyd | (4.4) |
C0Dαtξ1=γ1S1ϕ1(ˆx1)−κ1ξ1 | (4.5) |
where c1>0 and κ1>0 are known constants.
Introduce dynamic surface filter in [15] as
σ1C0Dαtυ1+υ1=τ1,υ1(0)=τ1(0) | (4.6) |
where σ1 is a constant.
By using (4.2) and (4.6), one has
C0Dαtη1=C0Dαtυ1−C0Dαtτ1=−η1σ1+W1(⋅) | (4.7) |
where W1(⋅) is a continuous function.
Remark 2: In the backstepping ETC design of FONSs, it is difficult to obtain the mathematical analytical expression of the fractional derivative of the virtual controllers. To solve this problem, some authors used the packaged approximation technology in [18,19,20] to repeatedly approximate the virtual controllers. Because this method takes all the signals of the closed-loop system as the input variables of the NN or FLS, it will increase the dimensions of the adjusted parameter vector, resulting in the problem of computational complexity. Therefore, this paper adopts the DSC technology to effectively avoid this problem.
Step i: From (3.5) and (4.1), one has
C0DαtSi=C0Dαtˆxi−C0Dαtυi−1=Si+1+ηi+τi+ξTiϕi(ˆˉxi)+˜ξTiϕi(ˆˉxi)−˜ξTiϕi(ˆˉxi)−C0Dαtυi−1+kie1 | (4.8) |
The Lyapunov function candidate is chosen as
Vi=Vi−1+12S2i+12γi˜ξTi˜ξi+12η2i−1 | (4.9) |
where γi>0 is a known constant.
The virtual controller τi and the adaptive law C0Dαtξi are designed as
τi=−ciSi−Si−Si−1−ξTiϕi(ˆˉxi)+C0Dαtυi−1−kie1 | (4.10) |
C0Dαtξi=γiSiϕi(ˆˉxi)−κiξi | (4.11) |
where ci>0 and κi>0 are known constants.
Introduce dynamic surface filter as
σiC0Dαtυi+υi=τi,υi(0)=τi(0) | (4.12) |
where σi is a constant.
By using (4.8) and (4.12), one can obtain
C0Dαtηi=C0Dαtυi−C0Dαtτi=−ηiσi+Wi(⋅) | (4.13) |
where Wi(⋅) is a continuous function.
Step n: We first devise an event-triggered controller as
τn=−cnSn−kne1−ξTnϕn(ˆˉxn)−Sn−1+C0Dαtυn−12Sn | (4.14) |
ω(t)=−(1+ˉδ)(τntanh(Snτnψ)+ˉmtanh(Snˉmψ)) | (4.15) |
u(t)=ω(tk),∀t∈[tk,tk+1) | (4.16) |
where cn>0 is a known constant, and tk(k∈z+) defines input updating time.
Thus, in order to get a lower communication rate, the event-triggered condition can be designed as
tk+1=inf{t∈R||ν(t)|≥ˉδ|u(t)|+m} | (4.17) |
where ˉδ∈(0,1),m>0 and ˉm>[m/(1−ˉδ)] are given as the known parameters, and ν(t)=ω(t)−u(t) is called as the measurement error. When (4.17) is triggered, the time will be marked as tk+1, and the controller u(tk+1) will be utilized to the system. At the time t∈[tk,tk+1) the control signal is always unchanging.
In order to discuss the event-triggered rule, we consider that the actuator normally operates, i.e., |ω(t)−u(t)|≤ˉδ|u(t)|+m.
If v(tk)>0, the measured error can be rewritten as
−ˉδu(tk)−m≤ω(t)−u(t)≤ˉδu(tk)+mu(t)−ω(t)=λ1(ˉδu(tk)+m) | (4.18) |
where λ1(t)∈[−1,1].
If v(tk)<0, we can transform the event-triggered condition (4.17) as
ˉδu(tk)−m≤ω(t)−u(t)≤−ˉδu(tk)+mu(t)−ω(t)=λ2(ˉδu(tk)−m) | (4.19) |
where λ2(t)∈[−1,1].
From (4.18) and (4.19), one obtains
ω(t)=u(t)+ˉδλ1(t)u(t)+λ2(t)m | (4.20) |
where |λi|≤1,i=1,2 are time-varying variables. Then, one has
u(t)=ω(t)1+λ1(t)ˉδ−λ2(t)m1+λ1(t)ˉδ | (4.21) |
Remark 3: The event-triggered parameters ˉδ and m in (4.17) are determined according to the required communication rate. Therefore, in practical applications, while ensuring satisfactory tracking performance, we should try to reduce the communication burden.
According to (3.5), (4.1) and (4.21), one has
C0DαtSn=C0Dαtˆxn−C0Dαtυn−1=kne1+ξTnϕn(ˆˉxn)+ω(t)1+λ1(t)ˉδ−λ2(t)m1+λ1(t)ˉδ+˜ξTnϕn(ˆˉxn)−C0Dαtυn−1−˜ξTnϕn(ˆˉxn), | (4.22) |
Choose the Lyapunov function as
V=Vn−1+12S2n+12η2n−1+12γn˜ξTn˜ξn, | (4.23) |
where γn>0 is a known constant.
Assumption 2 [10,12]: For any initial conditions, there exists a constant q>0, such that V(0)≤q.
The adaptive law C0Dαtξn is designed as:
C0Dαtξn=γnSnϕn(ˆˉxn)−κnξn | (4.24) |
where κn>0 is a known constant.
Remark 4: A backstepping control algorithm is indicated for FONSs in [17]. It applies the stability analysis of integer-order Lyapunov methods to known fractional-order systems. However, in this article, the system model may be completely unknown. In addition, the stability of the control algorithm is analyzed by the fractional order adaptive stability criterion.
Theorem 2: Consider System (2.1), under Assumptions 1–2, and then the put forward adaptive fuzzy output feedback event-triggered controller (4.21) with the event-triggered mechanism (4.17) can keep that controlled fractional-order system is stable, and the tracking error is able to regulate to a small residual set of the origin. Meanwhile, Zeno behavior is removed effectively.
Proof: Construct the whole Lyapunov function as
V=V0+n∑i=1Vi=V0+n∑i=1(12S2i+12γi˜ξTi˜ξi)+n−1∑i=112η2i | (4.25) |
By utilizing the inequality C0Dαt(xT(t)x(t))/2≤xT(t)C0Dαtx(t), one can obtain
C0DαtV≤C0DαtV0+n∑i=1(SiC0DαtSi+1γi˜ξTiC0Dαt˜ξi)+n−1∑i=1ηiC0Dαtηi | (4.26) |
According to (4.4), (4.10), (4.14), (4.22), (4.23), (4.26) and adding and subtracting Snτn, |Snˉm| in the right of (4.26), the following equality can be obtained:
S1C0DαtS1=S1(e2+S2+η1+τ1+ξ∗T1(ϕ1(x1)−ϕ1(ˆx1))+ξT1ϕ1(ˆx1)+˜ξT1ϕ1(ˆx1)−C0Dαtyd+ε1), | (4.27) |
SiC0DαtSi=Si(Si+1+ηi+τi+ξTiϕi(ˆˉxi)+˜ξTiϕi(ˆˉxi)−˜ξTiϕi(ˆˉxi)−C0Dαtυi−1+kie1), | (4.28) |
SnC0DαtSn=Sn(kne1+ξTnϕn(ˆˉxn)+ω(t)1+λ1(t)ˉδ−C0Dαtυn−1−λ2(t)m1+λ1(t)ˉδ+˜ξTnϕn(ˆˉxn)−˜ξTnϕn(ˆˉxn)+τn−τn)+|Snˉm|−|Snˉm|. | (4.29) |
In view of |λi(t)|≤1 and Snω(t)≤0, we can obtain
Snω(t)1+λ1(t)ˉδ≤Snω(t)1+ˉδ | (4.30) |
λ2m1+λ1(t)ˉδ≤|m1−ˉδ| | (4.31) |
According to (4.26), (4.30) and (4.31), (4.29) can be rewritten as
SnC0DαtSn≤Sn(kne1+ξTnϕn(ˆˉxn)−C0Dαtυn−1−τn+˜ξTnϕn(ˆˉxn)−˜ξTnϕn(ˆˉxn))+|Snτn|+|Snˉm|−Snτntanh(Snτnψ)−Snˉmtanh(Snˉmψ). | (4.32) |
Then, utilizing the inequality |τ|−τtanh(τ/ψ≤χψ), χ=0.2785, one can get
SnC0DαtSn≤Sn(kne1+ξTnϕn(ˆˉxn)−C0Dαtυn−1−τn+˜ξTnϕn(ˆˉxn)−˜ξTnϕn(ˆˉxn))+0.557ε∗. | (4.33) |
For (4.14)–(4.17), (4.33) applying Young's inequality, one gets
S1(e2+ε1+ξ∗T1(ϕ1(x1)−ϕ1(ˆx1)))≤2S21+||e||22+ε∗212+||ξ∗1||2 | (4.34) |
Siηi≤S2i2+η2i2 | (4.35) |
−Si˜ξTiϕi(^¯xi))≤S2i2+˜ξTi˜ξi2 | (4.36) |
Substituting (4.9)–(4.11), (4.14)–(4.17), (4.10)–(4.31), (4.34)–(4.36) into (4.33) yields
C0DαtV≤−ˉλ||e||2+12||P||2n∑i=1˜ξTi˜ξi+n∑h=1(−chS2h+κhγh˜ξThξh)+n−1∑h=1(ηh(−ηhσh+ηh2+Wh))+n∑h=2˜ξTi˜ξi2+δ1+0.557ε∗ | (4.37) |
Note that Ξ0={y2d+(C0Dαtyd)2+(C0Dαt(C0Dαtyd))2≤Z0} and Ξ={V(t)≤q} are compact sets, and thus Ξ0×Ξ is still a compact set. Since Wi(⋅) are continuous functions on Ξ0×Ξ, there exist positive constants Ki such that |Wi(⋅)|≤Ki.
Applying Young's inequality again, yields:
˜ξThξh≤−12˜ξTh˜ξh+12||ξ∗h||2 | (4.38) |
ηhWh≤η2h2+K2h2 | (4.39) |
Substituting (4.38) and (4.39) into (4.37), one has
C0DαtV≤−ˉλ||e||2+12||P||2n∑i=1˜ξTi˜ξi+n−1∑h=1((1−1σh)η2h+K2h2)+δ1+n∑h=1(−κh2γh˜ξTi˜ξi−chS2h+κh2γh||ξ∗h||2+˜ξTi˜ξi2)+0.557ε∗ | (4.40) |
Then, we have
C0DαtV≤−μV+D | (4.41) |
where μ=min{2(ˉλ/λmax(P)),2ch,κh−γh(||P||2+1),2/σh−2}, and D=δ1+n−1∑h=1(K2h/2)+n∑h=1(κh/2γh)||ξ∗h||2+0.557ε∗.
Now, from (4.41) and according to Liu et al. [7] and Gong and Lan [22], one obtains
C0DαtV+β(t)=−μV+D | (4.42) |
where β(t)>0.
Applying the Lyapunov transform on (4.42) yields
V(s)=sα−1V(0)sα+μ+Ds(sα+μ)−β(s)sα+μ=sα−1V(0)sα+μ+sα−(α+1)Dsα+μ−β(s)sα+μ | (4.43) |
Using the inverse Laplace transform on (4.43), yields
V(t)=Eα,1(−μtα)V(0)+tαEα,α+1(−μtα)D−β(t)∗tα−1Eα,α(−μtα) | (4.44) |
where ∗ denotes the convolution operator.
Notably, β(t)≥0 and tα−1Eα,α(−μtα)≥0 in (4.44), so β(t)∗tα−1Eα,α(−μtα)≥0. Thus, one has from (4.44)
V(t)≤Eα,1(−μtα)V(0)+tαEα,α+1(−μtα)D | (4.45) |
From Lemma 1, it follows that
|tαEα,α+1(−μtα)D|≤Dtαd1+|μtα|≤Ddμ | (4.46) |
Therefore, for t≥0, it follows that
V(t)≤V(0)Eα,1(−μtα)+Ddμ | (4.47) |
Due to Lemma 1, one obtains
|Eα,1(−μtα)|≤λ1+μtα | (4.48) |
Then, one writes (4.48) as follows:
V(t)≤V(0)λ1+μtα+Ddμ | (4.49) |
From (4.49), it follows:
12S21≤V(t)≤V(0)λ1+μtα+Ddμ | (4.50) |
12eTPe≤V(t)≤V(0)λ1+μtα+Ddμ | (4.51) |
Therefore, one has
|S1|≤√2λV(0)1+μtα+2Ddμ | (4.52) |
‖e‖≤√2λV(0)1+μtα(λmin(P))+2Ddμ(λmin(P)) | (4.53) |
Based on (4.49), (4.52) and (4.53), we proved that the controlled system can be stable, and limt→∞|S1|=√2Dd/μ and limt→∞‖e‖=√2Dd/(μ(λmin(P))), which means that Si(i=1,...,n), e and ˜ξ are bounded. Furthermore, as ξ∗i is bounded, ξi as also bounded. Finally, by choosing design parameters, the tracking error and observer error are reduced.
Remark 5: From (4.46), it can be concluded that smaller tracking error can be obtained by increasing μ or decreasing D. Consequently, for smaller D, we can appropriately decrease κh or increase γh according on the definition of D=δ1+n−1∑h=1(K2h/2)+n∑h=1(κh/2γh)||ξ∗h||2+0.557ε∗. So as to get larger μ, we can appropriately increase ch and κh or decrease γh and σh by the definition of μ=min{2(ˉλ/λmax(P)),2ch,κh−γh(||P||2+1),2/σh−2}.
Ultimately, Zeno behavior is removed through the following proof. By recalling the measurement error ν(t)=ω(t)−u(t), we have
C0Dαt|ν|=C0Dαt√ν⋅ν=sign(ν)C0Dαtν≤|C0Dαtω| | (4.54) |
From (4.20) that ω(t) is a differentiable signal of order α, and C0Dαtω is a bounded function.
Thus, the existence of ρ>0 makes |C0Dαtω|≤ρ hold. According to ν(tk)=0 and limt→tk+1v(t)=m, one can have tk+1−tk≥m/ρ. So, Zeno behavior does not occur.
Remark 6: It is worth noting that the control schemes designed by the authors in [7,8,9,10,11,12,13,14] are based on time triggered control. Because the control signal is sampled and updated periodically, it leads to a waste of communication resources. In order to solve this issue, an event-triggered mechanism is introduced in the backstepping technology. This mechanism enables the control signal to be sampled and updated only when the given conditions cannot be met, thus decreasing the communication load.
Remark 7: The repeated differentiation of virtual control function will lead to complexity explosion, so filter is introduced to solve this problem. By using event-triggered mechanism and dynamic surface filter at the same time, this paper greatly saves the waste of computing resources.
Remark 8: In [15,16], it is important to study the adaptive ETC for integer-order nonlinear systems. However, we have designed an event-triggered rule for FONSs with unmeasurable states. Within the framework of event-triggered DSC scheme, we solved the computing explosion caused by duplicate derivation of virtual controllers. Unlike event-triggered rule in Wang et al. [17], threshold is a function of system state or tracking error. This paper determines the improved event-triggered mechanism based on the size of the control signal itself.
This part gives a simulation example to verify the availability of theoretical results.
Example: The fractional-order strict-feedback system is described as follows:
{C0Dαtx1=x2+(x1−x31)C0Dαtx2=u+20x1−x2y=x1 | (5.1) |
when f1(x1)=x1−x31,f2(x1,x2)=20x1−x2.
The membership functions can be chosen as
μAl1(x1)=e−(x1−2+l)216,μAl2(x2)=e−(x2−2+l)216,l=1,...,5 | (5.2) |
The given reference signal is yd=cos(2t). The observer gain is selected as K1=[k1,k2]T=[10,220]T. Then, the observer (3.3) can be written as
C0Dαtˆxi=Aˆxi+Ly+n∑i=1Biˆfi(ˆˉxi|ξi)+Buˆy=Cˆx1 | (5.3) |
Further, given Q=3I, a positive definite matrix P=[0.30140.01360.013666.4364] can be obtained by solving the Lyapunov Eq (3.2).
The control law can be given as
τ1=−c1S1−52S1−ξT1ϕ1(ˆx1)+C0Dαtydτ2=−c2S2−k2e1−ξT2ϕ2(^¯xi)−S1+C0Dαtυ1−12S2 | (5.4) |
The event-triggered controller is devised as
ω(t)=−(1+ˉδ)(τ2tanh(S2τ2ψ)+ˉmtanh(S2ˉmψ)). | (5.5) |
u(t)=ω(tk),∀t∈[tk,tk+1) | (5.6) |
The event-triggered condition can be designed as
tk+1=inf{t∈R||v(t)|≥ˉδ|u(t)|+m}. | (5.7) |
where ˉδ∈(0,1), m>0 and ˉm>[m/(1−ˉδ)]. With the following adaptive laws:
C0Dαtξ1=γ1S1ϕ1(ˆx1)−κ1ξ1C0Dαtξ2=γ2S2ϕ2(^¯xi)−κ2ξ2 | (5.8) |
In the simulation, choose the parameters as follows: α=0.98, c1=5, c2=15, κ1=0.01, κ2=0.02, ˉδ=0.45, ˉm=0.15 and ψ=0.4. The system states initial conditions are chosen as x1(0)=0.4, x2(0)=0.5, ˆx1(0)=0.5, ˆx2(0)=0.5, ξ1(0)=[−0.1,−0.3,−0.5,−0.7,−0.9]T and ξ2(0)=[−0.1,−0.3,−0.5,−0.7,−0.9]T.
The simulation results are shown in Figures 1–6. Figure 1 shows the curves of reference signal yd and the system output y. Figure 2 shows the curves of reference signal yd and the system output y without ETC. From Figures 1 and 2, we can see that ETC can ensure satisfactory system performance. The trajectories of the tracking error are shown in Figure 3. Figures 4 and 5 response of xi and ˆxi, i=1,2. Figure 6 responses of u. Figure 7 shows the trigger time intervals with the event-triggered control. However, by calculating, we know that the controller executes 2000 times without event-triggered control; under the event-triggered control method, the number of samples is only 1007, which greatly reduces the waste of communication resources. From Figures 1–7, it is concluded that the proposed event-triggered controller can achieve the stability of the controlled system and effectively decrease the communication load.
The observer-based adaptive ETC algorithm for FONS was investigated in this study. By employing FLS to model the unknown dynamics, a fuzzy state observer is constructed for the unmeasurable state vectors. Using an adaptive backstepping control algorithm, an observer-based adaptive fuzzy DSC method is proposed. The put forward control algorithm has avoided computational complexity problem resulted in the repeated iteration of virtual controllers in the inherent backstepping method. Additionally, it has reduced the burden of communication and removed the Zeno behavior. The simulation results testify the validity of the controller. The further research will focus on the intelligent adaptive ETC problem of fractional-order nonlinear impulsive systems based on this study and literature [23,24].
This work is supported in part by the National Natural Science Foundation of China (under Grant No. 62173172), and in part by the Doctoral Startup Fund of Liaoning University of Technology (under Grant No. XB2021015).
The authors declare that there is no conflict of interest.
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